Methods and apparatus for using taylor series expansion concepts to substantially reduce nonlinear distortion

ABSTRACT

Methods and apparatus are provided for substantially reducing and/or canceling nonlinearities of any order in circuits, devices, and systems such as amplifiers and mixers. In particular, methods and apparatus are provided for substantially reducing and/or canceling third order nonlinearities in circuits, devices, and systems such as amplifiers and mixers. A first coupler is used to split an input signal into two equal-amplitude in-phase components, each component is processed by two nonlinear devices with different nonlinearities, and a final combiner, such as a 180-degree hybrid, recombines the processed signals 180 degrees out of phase and substantially reduces and/or cancels the undesired nonlinear distortion components arising due to nonlinearities in the nonlinear devices.

CROSS-REFERENCE TO RELATED APPLICATIONS

[0001] This application is a divisional of U.S. application Ser. No.10/101,005, filed Mar. 19, 2002.

FIELD OF THE INVENTION

[0002] The present invention relates to electronic circuits, devices,and systems and the linearization of nonlinearites inherent in suchdevices and, more specifically, the present invention relates to methodsand apparatus for reduction, cancellation, and enhancement ofnonlinearities of electronic devices.

BACKGROUND OF THE INVENTION

[0003] Circuit and device nonlinearities are well known in the art tocreate undesired intermodulation distortion. In many applications, thesenonlinearities and associated intermodulation distortion of circuits anddevices limit the performance of systems and often lead to designs withincreased power consumption in efforts to avoid intermodulationdistortion. Example applications include the receiver and transmitterportions of cellular phone handsets, base stations, cable televisionhead-ends, cable television amplifiers, and general purpose amplifiers.In receivers, the presence of strong undesired signals, typically atnearby frequencies, can produce intermodulation products that interferewith the reception of weak desired signals. In transmitters,intermodulation distortion can lead to the generation of undesiredfrequency emissions that violate regulatory requirements and interferewith other services, typically at nearby frequencies.

[0004] For example, in cellular phones the problem of receiving weaksignals in the presence of strong signals is of considerable interest.It is common for a cellular phone to be situated far from a base-stationantenna tower (leading to a weak desired signal from the tower) whileother strong signals such as nearby cellular phones, televisiontransmitters, radar and other radio signals interfere with the receptionof the desired weak signal. This interference is further exacerbated bynonlinearities within electronic circuits, including third ordernonlinearities that are well known in the art to limit the performanceof circuits and devices.

[0005] In addition to the problems created by nonlinearities in radioreceivers, radio transmitters are similarly affected by third-order andother nonlinearities. Such nonlinearities in transmitters lead toundesired transmitter power in frequency bands outside the desiredtransmission frequency bands, such effects being commonly referred to asspectral re-growth in the art. These out-of-band signals in radiotransmitters can violate regulatory emission requirements and causeinterference with other users operating at nearby frequencies.

[0006] In broadband systems, such as cable television, nonlinearitiespresent particular problems since such systems have a plurality ofsignals (i.e., television signals) at relatively high power levels. Thisplurality of signals, combined with relatively high power levels, canlead to particular sensitivity to channel-to-channel interferenceproblems induced by nonlinearities in broadband and cable televisionapplications.

[0007] In addition, it is well known in the art that nonlinearities arealso used in a beneficial manner to achieve desired effects, and in suchcases enhancement of the nonlinearities is the desired outcome. Exampleapplications where such enhancement of nonlinearities is desirable areharmonic mixers and frequency multipliers.

[0008] The nonlinearities of devices, such as amplifiers, are commonlymodeled as Taylor series expansions, i.e., power series expansions orpolynomial expansions, of an input signal. For example, the outputvoltage y of a device may be described as a Taylor series, orpolynomial, expansion of the input voltage x:

y=a ₀ +a ₁ x+a ₂ x ² +a ₃ x ³+ . . .

[0009] where a₀, a₁, a₂, a₃ . . . are constants representative of thebehavior of the particular device being modeled, and the order of thepolynomial is determined by the highest power of x in the polynomialexpansion. In most situations, the linear term a₁x is the desired linearsignal, and the terms a_(n)x^(n), with n≠1, are undesired. The term a₀represents a constant, or DC (direct current), offset that is easilyremoved in most applications.

[0010] In radio applications, the term a₃x³ is particularly problematicwhen an input signal such as x=A cos(ω₁t)+A cos(ω₂ t) is considered. Inthis case the cubic term of the Taylor series is defined as:

a ₃ x ³ =a ₃ A ³[cos ³(ω₁ t)+3 cos ²(ω₁ t) cos(ω₂ t)+3 cos(ω₁ t)cos ²(ω₂t)+3 cos(ω₁ t)cos ²(ω₂ t)+cos ³(ω₂ t)]

[0011] where the terms cos ²(ω₁t)cos(ω₂t) and cos(ω₁t)cos ²(ω₁t) can befurther expanded to: $\begin{matrix}{{{\cos^{2}( {\omega_{1}t} )}\quad {\cos ( {\omega_{2}t} )}} = {\frac{1}{4}\lbrack {{2\quad {\cos ( {\omega_{2}t} )}} + {\cos ( {{2\quad \omega_{1}t} + {\omega_{2}t}} )} +} }} \\ \quad {\cos ( {{2\quad \omega_{1}t} - {\omega_{2}t}} )} \rbrack \\{{{\cos ( {\omega_{1}t} )}\quad {\cos^{2}( {\omega_{2}t} )}} = {\frac{1}{4}\lbrack {{2\quad {\cos ( {\omega_{1}t} )}} + {\cos ( {{2\quad \omega_{2}t} + {\omega_{1}t}} )} +} }} \\ \quad {\cos ( {{2\quad \omega_{2}t} - {\omega_{1}t}} )} \rbrack\end{matrix}$

[0012] where the terms cos(2ω₁t−ω₂t)/4 and cos(2ω₂t−ω₁t)/4 are wellknown in the art to present particular difficulty in the design ofcommunications equipment since they can produce undesired in-banddistortion products at frequencies close to the desired linear signalfrequencies. For example, at frequencies of ƒ₁=100 MHz and ƒ₂=100.1 MHz,with ω₁=2πƒ₁ and ω₂2=2πƒ₂, the undesired frequency component 2ω₁−ω₂ is afrequency of 99.9 MHz and 2ω₂−ω₁ is a frequency of 100.2 MHz. These twoundesired frequencies at 99.9 and 100.2 MHz are created by thethird-order nonlinearity of the polynomial (i.e., a₃x³), and are soclose to the desired linear signal frequencies of 100 and 100.1 MHz thatthey cannot easily be removed by filtering.

[0013] One prior art approach to the problem employs feedforwardcompensation wherein a distortion error signal is generated by takingthe difference between a first amplified and distorted signal, and asecond undistorted signal, and later subtracting the distortion errorsignal from the first amplified and distorted signal in order to removethe distortion components.

[0014] This prior art is illustrated in the schematic drawing of FIG. 1,in which an apparatus 10 incorporating feedforward compensation is shownby way of example. An input signal 12 is applied both to first amplifier14 and a first delay device 16. The time delay of the first delay deviceequals the time delay of the first amplifier. The output signal 18 ofthe first amplifier is attenuated by the attenuator 20. The outputsignal 22 of the first delay device is subtracted from the output signal24 of the attenuator in a first subtractor 26 resulting in error signal28. The output signal 18 of the first amplifier is also input to asecond delay device 30. The time delay of the second delay device equalsthe time delay of the second amplifier 32 that amplifies the errorsignal. The output signal 34 of the second amplifier is subtracted fromthe output signal 36 of the second delay in a second subtractor 38 toform the final output signal 40.

[0015] For illustrative purposes, an example input frequency spectrum 42is shown for input signal 12 comprised of two input spectral lines ofequal amplitude at different frequencies. The spectrum at the outputsignal 18 of the first amplifier 14 is illustrated in second spectrum 44where the two innermost spectral lines correspond to the original inputfrequencies illustrated in the input spectrum, but with largeramplitude, and the two outermost spectral lines representing third-orderdistortion components of the output signal 18 of the first amplifier.The spectrum at the error signal 28 is illustrated in third spectrum 46where the two spectral lines correspond to an attenuated version of thethird-order distortion components of the second spectrum 44 (the twooutermost spectral lines in the second spectrum). In the third spectrumthe attenuation of attenuator 20 has adjusted the signal to completelyeliminate the two innermost spectral components of the second spectrum.The spectrum at the output signal 34 of the second amplifier 32 isillustrated in fourth spectrum 48 where the two spectral linescorrespond to an amplified version of the third spectrum, where theamplitude of the spectral components in the fourth spectrum equals theamplitude of the two outermost spectral components of the secondspectrum. The spectrum at the final output signal 40 is illustrated inthe fifth spectrum 50 where the two spectral lines correspond to anamplified version of the input frequency spectrum and all distortionproducts in the second spectrum (the two outermost spectral lines insecond spectrum) are canceled and eliminated.

[0016] For examples similar to the one illustrated in FIG. 1, see, U.S.Pat. No. 5,489,875, issued on Feb. 6, 1996, in the name of inventorCavers, which describes an adaptive version of this well-known scheme,and a similar scheme is described in U.S. Pat. Nos. 5,157,346, and5,323,119, issued on Oct. 20, 1992 and Jun. 21, 1994, respectively, inthe name of inventors Powell et al. Similar approaches are disclosed inU.S. Pat. No. 4,379,994, Bauman, issued Apr. 12, 1983; U.S. Pat. No.4,879,519, Myer, issued Nov. 7, 1989; U.S. Pat. No. 4,926,136, Olver,issued May 15, 1990; U.S. Pat. No. 5,157,346, Powell et al., issued Oct.20, 1992; U.S. Pat. No. 5,334,946, Kenington, issued Aug. 2, 1994; andU.S. Pat. No. 5,623,227, Everline et al., issued Apr. 22, 1997.

[0017] However, these prior art approaches require delay lines, ofconsiderable physical size, to compensate for delay through theamplifiers. These approaches also require the availability ofundistorted reference signals and further rely on accurate generation ofthe distortion error signal. In many applications the undistorted signalmay not be available or may be of such a small power level as to beunusable in prior art applications. A further disadvantage of the priorart is that said distortion error signal contains amplified noisecomponents of the amplified and distorted signal that can degrade thenoise of the overall system, making the prior art unattractive forapplication in low noise systems such as radio receivers. In addition,the prior art approaches relate more directly to power amplifier devicesbecause of the aforesaid limitations. Therefore, a need exists tosubstantially reduce and/or cancel nonlinearities without the need fordelay lines, without the need for undistorted reference signals, andwithout the need for a distortion error signal, such distortion errorsignal containing only distortion components and not containingcomponents of the undistorted signal.

[0018] A second prior art approach to the problem employs push-pullcompensation as shown in FIG. 2. As shown the apparatus 60 comprises afirst hybrid splitter 62, first and second amplifiers 64, 66 and asecond hybrid splitter 68 that functions as a combiner. An input signal70 is first split into first and second coupled signals 72 and 74 byfirst hybrid splitter 62, wherein the second coupled signal is 180degrees out of phase with the first coupled signal. As is well known inthe art, the fourth port of both the first and second hybrid splittersare properly terminated with impedance matched terminating loads 76 and78. The first coupled signal is input to the first amplifier 64 and thesecond coupled signal is input to the second amplifier 66, with thefirst and second amplifiers being identical. The input-outputrelationship of the first and second amplifier, being identical, may beapproximated by a Taylor, or power, series. For illustration, let a₀ bezero in the Taylor series, and consider terms up to the fourth order.Then, denote the first coupled signal 72 to the first amplifier 64 as x,and denote the first output signal 80 of the first amplifier 64 as y₁.The first output signal 80 of the first amplifier 64 can then beapproximated as:

y ₁ =a ₁ x+a ₂ x ² +a ₃ x ³ +a ₄ x ⁴

[0019] Since the second coupled signal 74, being the input of the secondamplifier 66 is 180 degrees out of phase with the first coupled signal72 of the first amplifier 64, the second coupled signal 74 as input ofthe second amplifier 66 may be expressed as −x, i.e., the negative ofthe first coupled signal of the first amplifier. Accordingly, denote thesecond coupled signal 74 as −x and denote the second output signal 82 ofthe second amplifier 66 as y₂. Then, the second output signal 82 of thesecond amplifier 66 can then be approximated as:

y ₂ =−a ₁ x+a ₂ x ² +−a ₃ x ³ +a ₄ x ⁴

[0020] The final output signal 84 is formed by combining the twoamplifier signals in a second hybrid splitter 68, with a 180-degreephase shift of the second output signal 82 and with 0 degree phase shiftof the first output signal 80, effectively subtracting the second outputsignal 82 from the first output signal 80 to form the final outputsignal 84, to within a multiplicative constant, 1/{square root}{squareroot over (2)}, relating to the impedances of the ports, as is wellknown in the art. Using the foregoing notation, and denoting the finaloutput signal 84 as y₃, the final output signal is defined as:$y_{3} = {{\frac{1}{\sqrt{2}}( {y_{1} - y_{2}} )} = {\frac{1}{\sqrt{2}}( {{2a_{1}x} + {2a_{3}x^{3}}} )}}$

[0021] where the multiplicative factor 1/{square root}{square root over(2)} is included for power conservation in the common case where thesecond hybrid splitter 68 is a passive radio-frequency circuit, and allfour ports have the same impedance. The desired linear component of thefinal output signal 84 is the linear term in the Taylor seriesexpansion, represented in the term 2a₁x/{square root}{square root over(2)} in the expression for y₃ above. As is well known in the art, theeven order distortion terms, or nonlinearities, present in the amplifieroutput signals y₁ and y₂, i.e., the a₂x² and a₄x⁴ terms in the Taylorseries expansion, are eliminated in the final output signal 84. However,the odd order distortion terms, or nonlinearities, such as the2a₃x³/{square root}{square root over (2)} term in the expression for y₃above, are not eliminated in the final output signal 84. In addition,the method requires two identical amplifiers. Therefore, a need existsto develop methods and apparatus to eliminate odd order nonlinearities,such as the a₃x³ and a₅x⁵ terms in the Taylor series expansion ofnonlinear circuits, devices, and systems.

[0022] Other prior art approaches use an attenuator or automatic gaincontrol to reduce signal levels, thus resulting in reduction ofthird-order distortion at a rate faster than reduction of the desiredsignal levels (due to the cubic term in the Taylor series expansion).See for example, U.S. Pat. No. 4,553,105, Sasaki, issued Nov. 12, 1985;U.S. Pat. No. 5,170,392, Riordan, issued Dec. 8, 1992; U.S. Pat. No.5,339,454, Kuo et al., issued Aug. 16, 1994; U.S. Pat. No. 5,564,094,Anderson et al., issued Oct. 8, 1996; U.S. Pat. No. 5,697,081, Lyall,Jr. et al., issued Dec. 9, 1997: U.S. Pat. No. 5,758,271, Rich et al.,issued May 26, 1998; U.S. Pat. No. 6,044,253, Tsumura, issued Mar. 28,2000; U.S. Pat. No. 6,052,566, Abramsky et al., issued Apr. 18, 2000;U.S. Pat. No. 6,104,919, and Lyall Jr. et al., issued Aug. 15, 2000.Such approaches employing an attenuator or automatic gain control toreduce signal levels are not generally useful in receiver applicationswhere the attenuation can reduce signal-to-noise ratio of the desiredsignal, and such approaches are undesirable in transmitter applicationswhere it is desirable for power efficiency purposes to drive the poweramplifier at or near the rated output power capacity.

[0023] In U.S. Pat. No. 5,917,375, issued on Jun. 29, 1999, in the nameof inventors Lisco et al., delay lines and phase shifters are used toproduce in-phase desired signals with out-of phase third-orderdistortion signals, which when added together result in cancellation ofthe third-order distortion signals. A desired method and apparatus forcancellation of the third-order distortion will eliminate thephase-shift and delay methods taught in the Lisco et al. '375 patent,and will not require the generation of in-phase desired signalscomponents in conjunction with out-of phase third-order distortionsignal components.

[0024] In other patents; U.S. Pat. No. 5,151,664, issued in the name ofinventors Suematsu et al, on Sep. 29, 1992, requires an envelopedetection circuit. U.S. Pat. No. 5,237,332, issued in the name ofinventors Estrick et al, on Aug. 17, 1993 requires a cubing circuit thatgenerates only the cubic terms of the Taylor series and requires ananalog to digital conversion and complex weight and calibration signal.U.S. Pat. No. 5,774,018, issued in the name of inventors Gianfortune etal., on Jun. 30, 1998, requires a predistorter and delay line and isdesigned for large-signal power amplifier application. Additionalmethods and apparatus are disclosed in U.S. Pat. No. 5,877,653, issuedin the name of inventors Kim et al., on Mar. 2, 1999 that requirespredistortion, delay lines, employs the aforementioned variableattenuator methods, and also requires an undistorted reference signal.

[0025] Alternate methods and devices are taught in U.S. Pat. No.5,977,826, issued in the name of inventors Behan et al., on Nov. 2,1999, which requires a test signal and vector modulator. U.S. Pat. No.5,994,957, issued in the name of inventor Myer, on Nov. 30, 1999 teachesrequired delay lines and predistortion circuit. U.S. Pat. No. 6,198,346,issued in the name of inventors Rice et al., on Mar. 6, 2001 requiresmultiple feedforward loops, delay lines and phase shifters. U.S. Pat.No. 6,208,207, issued in the name of inventor Cavers, on Mar. 27, 2001requires three parallel signal paths, delay lines, and complex gainadjusters. U.S. Pat. No. 5,051,704, issued in the name of inventorsChapman et al., on Sep. 24, 1991, requires a pilot signal and leastmeans square circuit. U.S. Pat. No. 5,760,646, issued in the name ofinventors Belcher et al., requires a predistortion modulator.

[0026] Therefore, a need exists to develop methods and apparatus tosubstantially reduce and/or cancel nonlinearities in circuits, devices,and systems. In particular a desired need exists to reduce, remove,cancel, and eliminate odd order nonlinearities, such as the a₃x³ anda₅x⁵ terms in the Taylor series expansion of nonlinear circuits,devices, and systems. This need is especially apparent in radiocommunication systems such as cellular phones and in other relatedtechnical areas. The methods and apparatus should be capable of thenecessary function without the need to incorporate delay lines,undistorted reference signals and distortion error signals.Additionally, the means for reducing, canceling, eliminating orenhancing nonlinearities should be able to accomplish such with minimaladverse effect on noise figure and with minimal added noise.

[0027] Additionally, a specific need exists to reduce, remove, cancel,and eliminate third order nonlinearities from circuits, devices, andsystems, in particular amplifier circuits. Such reduction, removal andcancellation of nonlinear distortions will result in desired highquality amplification of signals. A more general need exists to reduce,remove, cancel, and eliminate any order nonlinearity from circuits,devices, and systems, such as amplifiers, mixers or the like.

[0028] Also, in those applications in which nonlinearities are used toachieve desired effects, enhancement of the nonlinearities is desired toimprove such devices and systems.

[0029] The desired means for reducing, canceling, eliminating and/orenhancing nonlinearities should be cost effective, thus eliminating theneed to implement costly high power devices such as amplifiers andmixers to achieve lowered levels of nonlinear distortion. Additionally,the desired means for reducing, canceling, eliminating and/or enhancingnonlinearities should provide for reduced power consumption, thusreducing the high power consumption typically associated with prior arthigh power devices such as amplifiers and mixers required to achievelowered levels of nonlinear distortion.

[0030] Another desired aspect of the means for reduction, cancellation,elimination and/or enhancement of the nonlinearities is to incorporatean adaptive means of reducing or canceling the nonlinear distortions,wherein the parameters of the methods used to affect reduction,cancellation, elimination or enhancement can be adjusted to effectcancellation of undesired nonlinearities.

[0031] A need exists to develop means and methods for reducing orcanceling nonlinear distortions in integrated circuit implementationswhere devices and components used in integrated circuits, such asamplifiers and mixers, can be accurately fabricated so as to effectreduction or cancellation of undesired nonlinearities. Examples of suchintegrated circuit devices include metal oxide field effect transistors,GaAs field effect transistors, bipolar transistors, diodes, and thelike. In particular, if the performance of one integrated circuit devicechanges from batch-to-batch or from chip-to-chip, the second integratedcircuit device, being integrated on the same chip, will typically haveperformance in track with the first integrated circuit device,preserving the desired reduction or cancellation. As is well known inthe art, scaling of devices on integrated circuits can be doneaccurately, permitting the control of relative parameters of devices andallowing effective integrated circuit implementation.

SUMMARY OF THE INVENTION

[0032] The present invention includes apparatus and methods forsubstantially reducing and/or canceling nonlinearities in circuits,devices, and systems. In particular the present invention substantiallyreduces and/or cancels odd order nonlinearities, such as the a₃x³ anda₅x⁵ terms in the Taylor series expansion of nonlinear circuits,devices, and system. The apparatus and methods of the present inventionsubstantially reduce and/or cancel nonlinearities without the need toincorporate delay lines, undistorted reference signals and distortionerror signals. Additionally, the present invention substantially reducesand/or cancels nonlinearities with minimal adverse effect on noisefigure and with minimal added noise. Specifically, the present inventionprovides means for reducing and/or canceling third order nonlinearitiesin circuits, devices, and systems, in particular amplifier or mixercircuits.

[0033] The present invention provides substantial reduction and/orcancellation of nonlinearities in a cost-effective manner, thuseliminating the need in current prior art to implement costly high powerdevices such as amplifiers and mixers to achieve lowered levels ofnonlinear distortion. Additionally, the present invention provides meansof substantially reducing and/or eliminating nonlinearities with reducedpower consumption, thus reducing the high power consumption typicallyassociated with prior art high power devices such as amplifiers andmixers required to achieve lowered levels of nonlinear distortion.

[0034] A first embodiment of the invention, an apparatus forsubstantially reducing and/or canceling nonlinear distortion, includes afirst coupler having an input and first and second outputs. The firstcoupler is capable of splitting an input signal into first and secondcoupled signals having equal amplitude and in-phase with respect to eachother. The apparatus also includes a first nonlinear device having aninput in communication with the first output of the first coupler and anoutput and a second nonlinear device having an input in communicationwith the second output of the first coupler and an output. The nonlineardevice will typically comprise an amplifier, a mixer or the like, withsubstantially equal time delay and phase. The apparatus also includes asecond coupler having a first input in communication with the output ofthe first nonlinear device, a second input in communication with theoutput of the second nonlinear device and an output. The second coupleris capable of 180-degree phase shifting an output signal of the secondnonlinear device and coupling the phase shifted output signal of thesecond nonlinear device with an output signal of the first nonlineardevice to generate a final output signal.

[0035] In this embodiment the second nonlinear device will typicallyhave a different gain and a different third order intercept point thanthe first nonlinear device. As such, the gain of the first nonlineardevice, the gain of the second nonlinear device, the predeterminednonlinearity of the first nonlinear device and the predeterminednonlinearity of the second nonlinear device are predetermined tosubstantially reduce and/or cancel the predetermined nonlinearity oforder n.

[0036] This embodiment may also be defined in terms of the followingequation, in which, the gain of the first nonlinear device is defined asG₁, the gain of the second nonlinear device is defined as G₂, the thirdorder output intercept point of the first nonlinear device is defined asOIP3₁ and the third order output intercept point of the second nonlineardevice is OIP3₂ such that the first and second nonlinear devices areprovided with substantially equal time delay and phase such that2(OIP3₁−OIP3₂)=3(G₁−G₂), where G₁ is not equal to G₂.

[0037] This embodiment may also be defined in terms of a Taylor seriesexpansion, in which, the first nonlinear device is provided such that ithas a Taylor series expansion describing the output signal voltage ofthe first nonlinear device, y₁, in terms of an input signal voltage ofthe first nonlinear device, x₁, as y₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁ ³+a₄x₁ ⁴ . . ., the second nonlinear device is provided such that it has a Taylorseries expansion describing the output signal voltage of the secondnonlinear device, y₂, in terms of an input signal voltage of the secondnonlinear device, x₂, as y₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . , suchthat nonlinearities of order n are substantially reduced or canceled bysetting a_(n)=b_(n), and a₁ does not equal b₁.

[0038] A second embodiment of the invention, an apparatus forsubstantially reducing and/or canceling nonlinear distortion, includesan input coupling means having an input and first and second outputs.The input coupling means is capable of splitting an input signal intofirst and second coupled signals that are in-phase with respect to eachother. The apparatus also includes a first nonlinear device having aninput in communication with the first output of the input coupling meansand an output and a second nonlinear device having an input incommunication with the second output of the input coupling means and anoutput. The nonlinear devices typically comprise amplifiers, mixers orthe like, with substantially equal time delay and phase. The apparatusalso includes a subtractor having a first input in communication withthe output of the first nonlinear device, a second input incommunication with the output of the second nonlinear device and anoutput. The subtractor is capable of subtracting an output signal of thesecond nonlinear device from the output of the first nonlinear device togenerate a final output signal.

[0039] In this embodiment the second nonlinear device will typicallyhave a different gain and a different third order intercept point thanthe first nonlinear device. As such, the gain of the first nonlineardevice, the gain of the second nonlinear device, the predeterminednonlinearity of the first nonlinear device and the predeterminednonlinearity of the second nonlinear device are predetermined to cancelthe predetermined nonlinearity of order n.

[0040] This embodiment may also be defined in terms of the followingequation, in which, the gain of the first nonlinear device is defined asG₁, the gain of the second nonlinear device is defined as G₂, the thirdorder output intercept point of the first nonlinear device is defined asOIP3₁, the third order output intercept point of the second nonlineardevice is defined as OIP3₂, and K=10 log₁₀(p₂/p₁), where p₁ is the inputsignal power level of the first nonlinear device and p₂ is the inputsignal power level of the second nonlinear device. In this applicationthe first and second nonlinear devices and the input coupling means areprovided such that 2(OIP3₁−OIP3₂)=3(G₁−G₂−K), where G₁ is not equalG₂+K.

[0041] This embodiment may also be defined in terms of the Taylor seriesexpansion, in which the first nonlinear device is provided such that ithas a Taylor series expansion describing the output signal voltage ofthe first nonlinear device, y₁, in terms of an input signal voltage ofthe first nonlinear device, x₁, as y₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁ ^(3 l +a) ₄x₁⁴ . . . , the second nonlinear device is provided such that it has aTaylor series expansion describing the output signal voltage of thesecond nonlinear device, y₂ in terms of an input signal voltage of thesecond nonlinear device, x₂, as y₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . ,the ratio, k, is provided such that k=x₂/x₁, where k is set by the inputcoupling means provided, such that nonlinearities of order n aresubstantially reduced and/or canceled by setting k=(a_(n)/b_(n))^(1/n).

[0042] A third embodiment of the invention, an apparatus forsubstantially reducing and/or canceling nonlinear distortion, includes anonlinear device having an input and an output. The nonlinear device hasa Taylor series expansion describing an output current, i₀, in terms ofan input voltage, v, as i₀=b₀+b₁v+b₂v²+b₃v³+b₄v⁴ . . . . The apparatusalso includes a nonlinear load having an input in communication with theoutput of the nonlinear device. The nonlinear load has a Taylor seriesexpansion describing a current through the nonlinear load, i_(L), interms of a terminal voltage, v_(L), as i_(L)=a₀+a₁v_(L)+a₂v_(L)²+a₃v_(L) ³+a₄v_(L) ⁴ . . . The nonlinear device and the nonlinear loadare provided such that b₀=a₀, b₁=ca₁, b₂=c²a ₂, b₃=c³a₃,b_(n)=c^(n)a_(n) where, c, is a constant, so that the output of thenonlinear device substantially reduces and/or eliminates nonlinearitiesof the nonlinear device and the nonlinear load.

[0043] In the third embodiment the nonlinear device may include a firstn-channel field effect transistor (FET) having a gate in communicationwith an input source, a source and well in communication with ground,and a drain in communication with an output. The nonlinear load mayinclude a second n-channel FET having a source and well in communicationwith the drain of the first n-channel FET, and a gate and drain incommon communication and a third n-channel FET having a source and wellin communication with the drain of the second n-channel FET, and a gateand drain in common communication with a power supply.

[0044] In the third embodiment the nonlinear device may include a firstnpn bipolar junction transistor (BJT) having a base in communicationwith an input source, an emitter in communication with ground and acollector in communication with an output. The nonlinear load mayinclude a second npn BJT having an emitter in communication with thecollector of the first npn BJT, and a base and collector in commoncommunication and a third npn BJT having an emitter in communicationwith a collector of the second npn BJT, and a base and collector incommon communication with a power supply.

[0045] In a fourth embodiment of the invention, an apparatus forsubstantially reducing and/or canceling nonlinear distortion, includes afirst nonlinear device having an input and an output and an inputcoupling means having an input in communication with the output of thefirst nonlinear device and first and second in-phase outputs. Theapparatus also includes a second nonlinear device having an input incommunication with the first in-phase output of the input coupling meansand an output and a subtractor having a first input in communicationwith the output of the second nonlinear device, a second input incommunication with the second in-phase output of the input couplingmeans and an output. The first and second nonlinear devices willtypically comprise amplifiers, mixers or the like, with substantiallyequal time delay and phase. The subtractor subtracts the output signalof the second nonlinear device from the second in-phase output of theinput coupler to generate a final output.

[0046] The fourth embodiment may also be defined in terms of the Taylorseries expansion, in which, the first nonlinear device is provided todefine a Taylor series expansion describing an output signal voltage,y₁, in terms of an input signal voltage, x₁, as y₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁³+a₄x₁ ⁴ . . . , the second nonlinear is provided to define a Taylorseries expansion describing an output signal voltage, y₂, in terms of aninput signal voltage, x₂, as y₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . , andthe ratio the first in-phase coupled signal voltage to the secondin-phase coupled voltage being k. Third order nonlinearities aresubstantially reduced and/or canceled by setting, k in the apparatussuch that a₃−a₃b₁k−2a₁a₂b₂k²−a₁ ³b₃k³=0, and such that a₁−a₁b₁k does notequal zero. Second order nonlinearities are substantially reduced and/orcanceled by setting, k, in the apparatus such that a₂−a₂b₁k−a₁ ²b₂k²=0,and such that a₁−a₁b₁k does not equal zero.

[0047] A fifth embodiment of the invention, an apparatus forsubstantially reducing and/or canceling nonlinear distortion, includesan input coupling means having an input and first and second outputsthat is capable of splitting an input signal into first and secondin-phase signals. The apparatus also includes a first nonlinear devicehaving an input in communication with the second output of the inputcoupling means and an output. The apparatus additionally includes asubtraction means having a first input in communication with the firstoutput of the input coupling means, a second input in communication withthe output of the first nonlinear device and an output. The subtractionmeans phase-shifts 180-degrees an output signal of the first nonlineardevice and combines such with the first in-phase signal to generate adifference signal. The apparatus of this embodiment also includes asecond nonlinear device having an input in communication with the outputof the subtraction means and an output. The first and second nonlineardevices will typically comprise amplifiers, mixers or the like, withsubstantially equal time delay and phase. The difference signal isprocessed at the second nonlinear device resulting in an output signalhaving substantially reduced and/or canceled nonlinear distortion.

[0048] This embodiment may also be defined in terms of a Taylor seriesexpansion, in which the first nonlinear device is provided to define aTaylor series expansion describing an output signal voltage, y₂, interms of an input signal voltage, x₂, as y₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴. . . , the second nonlinear device is provided to define a Taylorseries expansion describing an output signal voltage, y₁, in terms of aninput signal voltage, x₁, as y₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁ ³+a₄x₁ ⁴ . . . , andthe ratio, k, of the input voltage of the first nonlinear device to thevoltage of the first in-phase signal is a constant value provided by theinput coupling means. Third order nonlinearities are substantiallyreduced and/or canceled by setting, k such that2a₂b₁b₂k³−2a₂b₂k²−a₁b₃k³+a₃−3a₃b₁k+3a₃b₁ ²k²−a₃b₁ ³k³=0, and such thata₁−a₁b₁k does not equal zero. Second order nonlinearities aresubstantially reduced and/or canceled by setting, k, such that a₂b₁²k²−a₁b₂k²−2a₂b₁k+a₂=0, and such that a₁−a₁b₁k does not equal zero.

[0049] A sixth embodiment of the invention, an apparatus forsubstantially reducing and/or canceling nonlinearities, includes a firstand second differential subcircuit. The first differential subcircuitincludes a first n-channel field-effect transistor (FET) having a gatein communication with a first bias voltage source, a source incommunication with ground and a drain and a first differential pair thatincludes second and third n-channel FETs. The second n-channel FEThaving a gate in communication with a positive terminal of adifferential input source, a source in communication with the drain ofthe first n-channel FET and a drain in communication with a negativeterminal of a differential output. The third n-channel FET having a gatein communication with a negative terminal of the differential inputsource, a source in communication with the drain of the first n-channelFET and a drain in communication with a positive terminal of thedifferential output. The second differential subcircuit includes afourth n-channel FET having a gate in communication with a second biasvoltage source, a source in communication with ground and a drain and asecond differential pair that includes fifth and sixth n-channel FETs.The fifth n-channel FET having a gate in communication with the positiveterminal of the differential input source, a source in communicationwith the drain of the fourth n-channel FET and a drain in communicationwith the positive terminal of the differential output. The sixthn-channel FET having a gate in communication with the negative terminalof the differential input source, a source in communication with thedrain of the fourth n-channel FET and a drain in communication with thenegative terminal of the differential output. The apparatus alsoincludes a first load resistor electrically connected between a powersupply and the drains of the second and sixth n-channel FETs and asecond load resistor electrically connected between the power supply andthe drains of the third and fifth n-channel FETs. A differential inputsignal is connected in-phase to the first and second differentialsubcircuits such that an output of the first differential subcircuit issubtracted from the output of the second differential subcircuit tosubstantially reduce and/or cancel third order nonlinearities.

[0050] In this embodiment the gain of the first differential subcircuit,the gain of the second differential subcircuit, a predetermined orderoutput intercept point of the first differential subcircuit and apredetermined order intercept point of the second differentialsubcircuit may be predetermined such that a predetermined ordernonlinearity is substantially reduced and/or canceled.

[0051] This embodiment may also be defined in terms of the followingequation, in which a gain of the first differential subcircuit isdefined as G₁, the gain of the second differential subcircuit is definedas G₂, the third order output intercept point of the first differentialsubcircuit is defined as OIP3₁, and the third order output interceptpoint of the second differential subcircuit is defined as OIP3₂, suchthat the first and second differential subcircuits are provided suchthat 2(OIP3₁−OIP3₂)=3(G₁−G₂) to substantially reduce and/or cancel thirdorder nonlinear distortion, where G₁ is not equal to G₂.

[0052] A seventh embodiment of the present invention, an apparatus forsubstantially reducing and/or canceling nonlinear distortion, includesan input coupling means having an input and first and second outputs.The input coupling means splits an input signal into a first and secondin-phase coupled signals. The device also includes a first nonlinearhaving an input in communication with the first output of the inputcoupling means and an output and a second nonlinear device having aninput in communication with the second output of the input couplingmeans and an output. The first and second nonlinear devices willtypically comprise amplifiers, mixers or the like, with substantiallyequal time delay and phase. The apparatus also includes a secondcoupling means having a first input in communication with the output ofthe first nonlinear device, a second input in communication with theoutput of the second nonlinear device and an output, wherein the secondcoupling means 180-degree phase shifts and multiplies by a constantfactor, k₂, an output signal of the second nonlinear device and combinessuch with the output of the first nonlinear device.

[0053] In this embodiment of the invention the gain of the firstnonlinear device, the gain of the second nonlinear device, thepredetermined nonlinearity of the first nonlinear device and thepredetermined nonlinearity of the second nonlinear device may bepredetermined to substantially reduce and/or cancel the predeterminednonlinearity of order n.

[0054] This embodiment of the invention may also be defined in terms ofan equation, in which, a gain of the first nonlinear device is definedas G₁ dB, a gain of the second nonlinear device is defined as G₂ dB, athird order output intercept point of the first nonlinear device isdefined as OIP3₂ dBm and a third order output intercept point of thesecond nonlinear device is OIP3₂ dBm, such that K1=10 log₁₀(p₂/p₁),where p₁ is the input signal power level of the first nonlinear deviceand p₂ is the input signal power level of the second nonlinear device,K2=20 log₁₀(k₂), where k₂ is the aforementioned multiplicative factorestablished by the second coupling means. The input coupling means, thesecond coupling means, and the first and second nonlinear devices areprovided such that 2(OIP3₁−OIP3₂−K2)=3(G₁−G₂−K1−K2), and where G₁ is notequal to G₂+K1+K2.

[0055] This embodiment of the invention may also be defined in terms ofa Taylor series equation, in which the first nonlinear device isprovided such that it has a Taylor series expansion describing theoutput signal voltage of the first nonlinear device, y₁, in terms of aninput signal voltage of the first nonlinear device, x₁, asy₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁ ³+a₄ ^(x) ₁ ⁴ . . . , the second nonlinear deviceis provided such that it has a Taylor series expansion describing theoutput signal voltage of the second nonlinear device, y₂, in terms of aninput signal voltage of the second nonlinear device, x₂, asy₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . , where the ratio k₁=x₂/x₁. Theratio k₂ is the aforementioned multiplicative factor established by thesecond coupling means. Nonlinearities of order n are substantiallyreduced and/or canceled by setting a_(n)−k₂b_(n)k₁ ^(n)=0, and such thata₁−k₂b₁k₁ does not equal zero.

[0056] This embodiment of the invention may also include an adaptivecontrol and feedback means having an input in communication with theoutput of the second coupling means, a first output in communicationwith the first coupling means, a second output in communication withfirst nonlinear device, a third output in communication with the secondnonlinear device and a fourth output in communication with the secondnonlinear device. The adaptive control and feedback means controls thenonlinearity, gain and phase of the first and second coupling means andthe first and second nonlinear devices.

[0057] An eighth embodiment of the invention, an apparatus forsubstantially reducing and/or canceling nonlinear distortion, includes afirst nonlinear device having an input and an output and a secondnonlinear device having an input and an output, the inputs of the firstand second nonlinear devices are in communication with an input signal.The apparatus also includes an attenuator having an input incommunication with output of the first nonlinear device and an outputand a first subtractor having a first input in communication with theoutput of the second nonlinear device, a second input in communicationwith the output of the attenuator and an output. The first subtractorsubtracts an output of the second nonlinear device from an output of theattenuator. Additionally, the apparatus includes a third nonlineardevice having an input in communication with the output of the firstnonlinear device and an output and a fourth nonlinear device having aninput in communication with output of the first subtractor and anoutput. Also, the apparatus includes a second subtractor having a firstinput in communication with the output of the third nonlinear device, asecond input in communication with the output of the fourth nonlineardevice and an output. The second subtractor subtracts the output of thefourth nonlinear device from the output of the third nonlinear device toform a final output signal.

[0058] In this embodiment the first nonlinear device and the secondnonlinear device may be of equal time delay and phase, the third andfourth nonlinear devices may be equal in time delay and phase, andpredetermined order nonlinearities are substantially reduced and/orcanceled in the final output signal by predetermined selection ofattenuation in the attenuator and predetermined selection of the gain,nonlinearity, and intercept points of the first, second, third andfourth nonlinear devices. In addition, predetermined ordernonlinearities are substantially reduced and/or canceled in the finaloutput signal by predetermined selection of the attenuation in theattenuator and predetermined selection of a Taylor series expansion ofthe first, second, third and fourth nonlinear devices.

[0059] This embodiment of the invention may also be defined in terms ofa Taylor series expansion, in which, the first nonlinear device isprovided such that it has a Taylor series expansion describing theoutput signal of the first nonlinear device, y₁, in terms of an inputsignal of the first nonlinear device, x₁, as y₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁³+a₄x₁ ⁴ . . . The second nonlinear device is provided such that it hasa Taylor series expansion describing the output signal of the secondnonlinear device, y₂ in terms of an input signal of the second nonlineardevice, x₂, as y₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . The third nonlineardevice is provided such that it has a Taylor series expansion describingthe output signal of the third nonlinear device, y₃ in terms of an inputsignal of the third nonlinear device, x₃, as y₃=c₀+c₁x₃+c₂x₃ ²+c₃ ³+c₄x₃⁴ . . . The fourth nonlinear device is provided such that it has aTaylor series expansion describing the output signal of the fourthnonlinear device, y₄ in terms of an input signal of the fourth nonlineardevice, x₄, as y₄=d₀+d₁x₄+d₂x₄ ²+d₃x₄ ³+d₄x₄ ⁴ . . . The ratio, k, isprovided such that k equals the ratio of the output signal of theattenuator to the input signal of the attenuator. Third order nonlineardistortion is substantially reduced and/or canceled by setting b₁³d₃+b₃d₁+2a₁b₂d₂k−2b₁b₂d₂−2a₁a₂d₂k²+3a₁ ²b₁d₃k²−3a₁b₁²d₃k−a₁d₃k³+2₁a₂c₂+a₁ ³c₃+a₃c₁+2a₂b₁d₂k−a₃d₁k=0, and such thatb₁d₁+a₁c₁−a₁d₁k≠0.

[0060] Alternatively, this embodiment of the invention is defined wheresecond order nonlinear distortion is substantially reduced and/orcanceled by setting b₂d₁+a₁ ²c₂−b₁ ²d₂+2a₁b₁d₂k+a₂c₁−a₁ ²d₂k²−a₂d₁k=0,and such that b₁d₁+a₁c₁−a₁d₁k≠0.

[0061] In a ninth embodiment of the present invention, an apparatus forsubstantially reducing and/or canceling nonlinear distortion includes aninput coupling means having an input and first and second outputs. Theinput coupling means is capable of splitting an input signal into firstand second in-phase signals. The apparatus also includes a firstnonlinear device having an input in communication with the first outputof the in-phase coupling means and an output and a second nonlineardevice having an input in communication with the second output of thein-phase coupling means and an output. Additionally, the apparatus alsoincludes an attenuator having an input in communication with output ofthe first nonlinear device and an output and a second coupling meanshaving a first input in communication with the output of the secondnonlinear device, a second input in communication with the output of theattenuator and an output. The second coupling means combines a180-degree phase-shifted and attenuated output of the second nonlineardevice with an output of the attenuator. The apparatus also includes athird nonlinear device having an input in communication with output ofthe first nonlinear device and an output and a fourth nonlinear devicehaving an input in communication with the output of the second couplingmeans and an output. The apparatus also includes a third coupling meanshaving a first input in communication with the output of the thirdnonlinear device, a second input in communication with the output of thefourth nonlinear device and an output. The third coupling means combinesa 180 degree phase shifted and attenuated output of the fourth nonlineardevice with the output of the third nonlinear device to form a finaloutput signal.

[0062] In this embodiment, predetermined order nonlinearities of order nare substantially reduced and/or canceled in the final output signal bypredetermined selection of the attenuation in the attenuator, couplingcoefficients of the first, second, and third couplers, and Taylor seriesexpansion of the first, second, third and fourth nonlinear devices.

[0063] Thus, the present invention involves apparatus and methods forsubstantially reducing and/or canceling nonlinearities in circuits,devices, and systems. In particular the present invention substantiallyreduces and/or cancels and eliminates odd order nonlinearities, such asthe a₃x³ and a₅x⁵ terms in the Taylor series expansion of nonlinearcircuits, devices, and systems. The apparatus and methods of the presentinvention substantially reduce and/or cancel nonlinearities without theneed to incorporate delay lines, undistorted reference signals anddistortion error signals. Additionally, the present inventionsubstantially reduces and/or cancels nonlinearities with minimal adverseeffect on noise figure and with minimal added noise. Specifically, thepresent invention provides means for substantially reducing and/orcanceling third order nonlinearities in circuits, devices, and systems,in particular amplifier or mixer circuits.

BRIEF DESCRIPTION OF THE DRAWINGS

[0064] Having thus described the invention in general terms, referencewill now be made to the accompanying drawings, which are not necessarilydrawn to scale, and wherein:

[0065]FIG. 1 illustrates a schematic drawing of feedforwardcancellation/elimination of nonlinearity techniques, in accordance withthe prior art.

[0066]FIG. 2 illustrates a schematic drawing of an apparatus forcancellation/elimination of even-order nonlinear distortion, inaccordance with the prior art.

[0067]FIG. 3 illustrates a schematic drawing of an apparatus forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention.

[0068]FIG. 4 illustrates a schematic drawing of an apparatus forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention.

[0069]FIG. 5 depicts a flow diagram of a method for substantiallyreducing and/or canceling third order nonlinear distortion, inaccordance with an embodiment of the present invention.

[0070]FIG. 6 illustrates flow diagram of a method for substantiallyreducing and/or canceling nonlinear distortion, in accordance with anembodiment of the present invention.

[0071]FIG. 7 illustrates a schematic diagram of an apparatus forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention.

[0072]FIG. 8 illustrates a schematic diagram of a specific apparatus forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention.

[0073]FIG. 9 illustrates a schematic diagram of a specific apparatus forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention.

[0074]FIG. 10 illustrates a flow diagram of a method for substantiallyreducing and/or canceling nonlinear distortion, in accordance with anembodiment of the present invention.

[0075]FIG. 11 illustrates a schematic diagram of an apparatus forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention.

[0076]FIG. 12 illustrates a schematic diagram of an apparatus forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention.

[0077]FIG. 13 illustrates a flow diagram of a method for substantiallyreducing and/or canceling nonlinear distortion, in accordance with anembodiment of the present invention.

[0078]FIG. 14 illustrates a flow diagram of a method for substantiallyreducing and/or canceling nonlinear distortion, in accordance with anembodiment of the present invention.

[0079]FIG. 15 illustrates test data, in accordance with an embodiment ofthe present invention.

[0080]FIG. 16 illustrates test data, in accordance with an embodiment ofthe present invention.

[0081]FIG. 17 illustrates a schematic diagram of an apparatus forsubstantially reducing and/or canceling nonlinear distortions, inaccordance with an embodiment of the present invention.

[0082]FIG. 18 illustrates a schematic diagram of an apparatus forsubstantially reducing and/or canceling nonlinear distortions, inaccordance with an embodiment of the present invention.

[0083]FIG. 19 illustrates a schematic diagram of an apparatus forsubstantially reducing and/or canceling nonlinear distortions, inaccordance with an embodiment of the present invention.

[0084]FIG. 20 illustrates a schematic diagram of an apparatus forsubstantially reducing and/or canceling nonlinear distortions, inaccordance with an embodiment of the present invention.

[0085]FIG. 21 illustrates a flow diagram of a method for substantiallyreducing and/or canceling nonlinear distortion, in accordance with anembodiment of the present invention.

DETAILED DESCRIPTION OF THE INVENTION

[0086] The present invention now will be described more fullyhereinafter with reference to the accompanying drawings, in whichpreferred embodiments of the invention are shown. This invention may,however, be embodied in many different forms and should not be construedas limited to the embodiments set forth herein; rather, theseembodiments are provided so that this disclosure will be thorough andcomplete, and will fully convey the scope of the invention to thoseskilled in the art. Like numbers refer to like elements throughout.

[0087] In accordance with an embodiment of the present invention, FIG. 3illustrates a schematic drawing of an apparatus for substantiallyreducing and/or eliminating nonlinear distortion in devices. The circuit100 includes an in-phase splitter 102, a first nonlinear device, such asfirst amplifier 104, a second nonlinear device, such as second amplifier106 and a 180-degree out-of-phase combiner 108. The in-phase splitterand the 180-degree out-of-phase combiner are shown for purpose ofillustration as 180-degree hybrids, but can be implemented with otherdevices, as is known by those of ordinary skill in the art. Inoperation, the in-phase splitter 102 splits the input signal 110 intofirst and second equal-amplitude in-phase signals 112 and 114. The firstin-phase signal is applied as input to a first amplifier 104 and thesecond in-phase signal is applied as input to a second amplifier 106.The first amplified output signal 116 is combined with the secondamplified output signal 118 in the 180-degree out-of-phase combiner 108,such that the first amplified output signal 116 is combined with a 180degree phase shifted version of the second amplified output signal 118to generate the final output signal 120. The effect of the 180-degreeout-of-phase combiner is to subtract the second amplified output signalfrom the first amplified output signal to form the final output signal.Additionally, the fourth port of the in-phase splitter and the180-degree out-of-phase combiner, shown for purpose of illustration as180-degree hybrids, are terminated in matched impedance loads 122 and124.

[0088] The first and second amplifiers 104 and 106 are designed suchthat they have unequal gains, otherwise the final output signal 120would not include an amplified version of the input signal 110, sinceamplified components of the input signal would be canceled andeliminated upon recombination out-of-phase in the 180-degreeout-of-phase combiner 108. In addition to being designed for unequalgains, the first and second amplifiers are designed with substantiallyequal time delay and phase and such that one of their nonlineardistortion components, such as third order nonlinear distortion, of thefirst and second amplified output signals 116 and 118 has equalamplitudes at the outputs of the first and second amplifiers. In theparticular case of substantially reducing and/or canceling third orderdistortion, the first and second amplifiers are designed such that thethird order distortion components are equal at the first and secondamplified output signals. Additionally, amplifiers can be designed forvarying levels of distortion, including third order nonlineardistortion, by adjusting current and voltage bias levels of componentswithin the amplifier and by selection or design of the components usedwithin the amplifier.

[0089] For substantially reduced and/or canceled third ordernonlinearities in the output signal 120 in the embodiment of FIG. 3, thethird order output intercept points of the first amplifier 104 andsecond amplifier 106 are designed such that most nearly2(OIP3₁₀₄−OIP3₁₀₆)=3(G₁₀₄−G₁₀₆), where OIP3₁₀₄ and OIP3₁₀₆ are the thirdorder output intercept points in dBm of the first and second amplifiers104 and 106 respectively, and G₁₀₄ and G₁₀₆ are the gains in dB of thefirst and second amplifiers, respectively. Typically, it is desirable tohave G₁₀₄ much greater than G₁₀₆, or G₁₀₆ much greater than G₁₀₄, sothat the gain is not greatly reduced in the overall embodiment of FIG.3. As is well known by one practiced in the art, the embodiment of FIG.3 can be rearranged to perform the same function by interchanging thein-phase splitter 102 and 180-degree out-of-phase combiner 108 such thatfirst and second signals 112 and 114 are 180 degrees out of phase, andsuch that the first and second amplified output signals 116 and 118 arecombined in phase. As would be apparent to one practiced in the art, thenonlinear devices may be of differing type, for example the firstnonlinear device may be an amplifier and the second nonlinear device maybe a diode. As is also well known in the art, the amplifiers shown inFIG. 3 can be replaced by any other nonlinear device, such as mixers,multi-stage amplifiers, and the like, where such circuits are similarlycharacterized for gains G₁₀₄ and G₁₀₆ and third order output interceptpoints OIP3₁₀₄ and OIP3₁₀₆. As is also well known in the art, phaseadjusting means, bias adjusting means, and amplitude adjusting means canbe added to the apparatus of FIG. 3 to provide fine resolutionadjustment to more precisely cancel the undesired nonlinear distortions.

[0090] For illustrative purposes only in FIG. 3, the frequency spectrumof various signals are illustrated in input spectrum 130, first outputspectrum 132, second output spectrum 134, and final output spectrum 136.As an illustrative example, the input spectrum is shown for the inputsignal 110 comprising two input spectral lines of equal amplitude atdifferent frequencies. The spectrum at the first amplified output signal116 of the first amplifier 104 is illustrated in the first outputspectrum, where the two innermost spectral lines correspond to theoriginal input frequencies illustrated in the input spectrum, but withincreased amplitude, and the two outermost spectral lines representingthird-order distortion components of the first amplified output signal.The spectrum at the second amplified output signal 118 of the secondamplifier 106 is illustrated in the second output spectrum, where thetwo innermost spectral lines correspond to the original inputfrequencies illustrated in the input spectrum, but with increasedamplitude, and the two outermost spectral lines represent third-orderdistortion components of the second amplified output signal 118. Thegains and nonlinearities of the first and second amplifiers are adjustedsuch that the nonlinear distortion components of the first and secondoutput spectrum are of equal amplitude and in-phase, while the innermostspectral lines corresponding to linear components of the first andsecond output spectrum are of unequal amplitude. The spectrum of thefinal output signal 120 of the 180-degree out-of-phase combiner 108 isillustrated in the final output spectrum where the two spectral linescorrespond to an amplified version of the input spectrum and alldistortion products shown in the first and second output spectrum arecanceled and eliminated.

[0091] In an alternate embodiment of the invention, similar in schematicrepresentation to that shown in FIG. 3 and described above, thenonlinear devices, in this application the amplifiers are designed tosubstantially reduce and/or cancel nonlinearities of any desired order.As is well known in the art, amplifiers can be designed for varyinglevels of distortion, including third order nonlinear distortion, byadjusting current and voltage bias levels of components within theamplifier and by selection or design of the components used within theamplifier. The first amplifier 104 is designed such that it has a Taylorseries expansion describing the first amplified output signal 116,denoted as y₁=a₀+a₁x+a₂x²+a₃x³+a₄x⁴ . . . where the first amplifiedoutput signal (i.e., voltage, etc.) is denoted as y₁, and where thefirst signal 112, being the input signal (i.e., voltage, etc.) to thefirst amplifier, is denoted as x. The second amplifier 106 is designedsuch that it has a Taylor series expansion describing the secondamplified output signal 118, denoted as y₂=b₀+b₁x+b₂x²+b₃x³+b₄x⁴ . . .where the second amplified output signal is denoted as y₂, and where thesecond signal 114, being the input of the second amplifier, is denotedas x since the first signal 112 equals the second signal 114. Thecoefficients a₀, a₁, a₂, a₃, a₄ . . . describe the first amplifier andcoefficients b₀, b₁, b₂, b₃, b₄ . . . describe the second amplifier.Third order nonlinearity is then substantially reduced and/or canceledin the final output signal 120 by designing the first and secondamplifiers such that most nearly a₃−b₃=0, or a₃=b₃. To retain thedesired linear output signal components, the first and second amplifiersare also designed such that a₁−b₁ does not equal zero. Typically, it isdesirable to have a₁ much greater than b₁, or alternatively b₁ muchgreater than a₁, so that the gain is not greatly reduced in the overallembodiment of FIG. 3.

[0092] Similarly, other order nonlinearities can be substantiallyreduced and/or canceled using the foregoing method. In particular, thesecond order nonlinearity can be substantially reduced and/or canceledby selecting most nearly a₂−b₂=0, or a₂=b₂. Alternatively, the fourthorder nonlinearity can be substantially reduced and/or canceled byselecting most nearly a₄−b₄=0, or a₄=b₄. Higher order nonlinearities oforder n can also be substantially reduced and/or canceled with the samedesign methods by using Taylor series expansions to higher order terms,and canceling the undesired order nonlinearity by setting a_(n)=b_(n).As is well known by one practiced in the art, the embodiment of FIG. 3can be rearranged to perform the same function for odd order products byinterchanging the in-phase splitter 102 and 180-degree out-of-phasecombiner 108 such that the first and second signals 112 and 114 are 180degrees out of phase, and such that first and second amplified outputsignals 116 and 118 are combined in phase. As is well known in the art,the amplifiers shown in FIG. 3 can be replaced by any other nonlineardevice, such as mixers, multi-stage amplifiers, and the like, where suchnonlinear devices are similarly characterized for their Taylor seriesexpansion. Additionally, phase adjusting means, bias adjusting means andamplitude adjusting means can be added to provide fine resolutionadjustment to more precisely cancel the undesired nonlinear distortions.

[0093]FIG. 4 illustrates a schematic representation of an apparatus forsubstantially reducing and/or canceling nonlinearities, in accordancewith another embodiment of the present invention. The apparatus 140includes a coupling means 142, a first nonlinear device, such as firstamplifier 144, a second nonlinear device, such as second amplifier 146and a subtractor 148. The coupling means 142 splits the input signal 150into first and second in-phase signals 152 and 154. The coupling meansresults in second in-phase signal (i.e., voltage, etc.) that is aconstant factor, k, times the first in-phase signal. The first in-phasesignal is applied as input to the first amplifier 144, and the secondin-phase signal is applied as input to the second amplifier 146. A firstamplified output signal 156 of the first amplifier is combined with thesecond amplified output signal 158 of the second amplifier in asubtractor 148, such that the second amplified output signal 158 issubtracted from the first amplified output signal 156 to generate thefinal output signal 160.

[0094] The first and second amplifiers 144 and 146 and the couplingfactor, k, of the coupling means 142 are designed such that the inputsignal 150 is not canceled and eliminated in the subtractor 148. Inaddition, the first and second amplifiers, and the coupling means, aredesigned with substantially equal time delay and phase and such that oneof the nonlinear distortion components, i.e., third order nonlineardistortion, of first and second amplified output signals 156 and 158 hasequal amplitudes at the outputs of the first and second amplifiers. Inthe particular embodiment of the invention in which third orderdistortion is substantially reduced and/or canceled in the final outputsignal 160, the first and second amplifiers 144 and 146, and thecoupling means 142, are designed such that the third order distortioncomponents are equal at the first and second amplified output signals156 and 158. As is well known in the art, amplifiers can be designed forvarying levels of distortion, including third order nonlineardistortion, by adjusting current and voltage bias levels of componentswithin the amplifier and by selection or design of the components usedwithin the amplifier. In addition, the coupling means can be readilydesigned by one practiced in the art using unequal power dividers,resistive networks, and the like. In addition, the subtractor can bereadily designed by one practiced in the art using 180-degree hybrids,cross-coupled collectors in integrated circuit bipolar transistordifferential amplifiers, cross-coupled drains in integrated circuitmetal-oxide field-effect transistor differential amplifiers, and thelike.

[0095] For substantially reduced and/or canceled third ordernonlinearities in the final output signal 160 the third order outputintercept points of the first and second amplifiers 144 and 146 aredesigned such that most nearly 2(OIP3₁₄₄−OIP3₁₄₆)=3(G₁₄₄−G₁₄₆−K), whereOIP3₁₄₄ and OIP3₁₄₆ are the third order output intercept points in dBmof the first and second amplifiers, respectively, and G,₁₄₄ and G₁₄₆ arethe gains in dB of first and second amplifiers, respectively, and K=10log₁₀(p₁₅₄/p₁₅₂) where p₁₅₂ and p₁₅₄ are the power levels in milliwattsof first and second in-phase signals 152 and 154 respectively.Typically, it is desirable to have G₁₄₄ much greater than G₁₄₆+K, orG₁₄₆+K much greater than G₁₄₄, so that the gain is not greatly reducedin the overall embodiment of FIG. 4.

[0096] As is well known by one practiced in the art, the embodiment ofFIG. 4 can be rearranged to perform the same function by interchangingthe coupling means 142 and subtractor 148 such that first and secondsignals 152 and 154 are 180 degrees out of phase, and such that firstand second amplified signals 156 and 158 are combined in phase. As iswell known in the art, the amplifiers shown in FIG. 4 can be replaced byany other nonlinear device, such as mixers, multi-stage amplifiers, andthe like, where such nonlinear devices are similarly characterized forgains G₁₄₄ and G₁₄₆ and third order output intercept points OIP3₁₄₄ andOIP3₁₄₆. As would be apparent to one practiced in the art, the nonlineardevices may be of differing type, for example the first nonlinear devicemay be an amplifier and the second nonlinear device may be a diode.Additionally, phase adjusting means, bias adjusting means and amplitudeadjusting means can be added to the FIG. 4 embodiment to provide fineresolution adjustment to more precisely cancel the undesired nonlineardistortions.

[0097] In an alternate embodiment of the invention, similar in schematicrepresentation to that shown in FIG. 4 and described above, theamplifiers are designed to substantially reduce and/or cancelnonlinearities of any desired order. The first amplifier 144 is designedsuch that it has a Taylor series expansion describing the firstamplified output signal 156, denoted as y₁=a₀+a₁x+a₂x²+a₃x³+a₄x⁴ . . .where the first amplified output signal (i.e., voltage, etc.) is denotedas y₁, and where the first in-phase signal 152, being the input signal(i.e., voltage, etc.) of the first amplifier, is denoted as x. Thesecond amplifier 146 is designed such that it has a Taylor seriesexpansion describing the second amplified output signal 158, denoted asy₂=b₀+b₁(kx)+b₂(kx)²+b₃(kx)³+b₄(kx)⁴ . . . where the second amplifiedoutput signal is denoted y₂, and where the second in-phase signal 154 isdenoted kx since the second in-phase signal equals the first in-phasesignal times a constant factor, k, where k is set by the design of thecoupling means 142. The final output is formed by the subtractor 148 togenerate the final output signal 160 that is the subtraction of thesecond amplified output signal from first amplified output signal. Thecoefficients a₀, a₁, a₂, a₃, a₄ . . . describe the first amplifier andcoefficients b₀, b₁, b₂, b₃, b₄ . . . describe the second amplifier.Third order nonlinearity is then substantially reduced and/or canceledin the final output signal by setting the coupling coefficient, k, inthe coupling means such that most nearly a₃−b₃k³=0, or k=(a₃/b₃)^(1/3).The desired linear output signal is then represented by the termsa₁x−b₁(kx)=(a₁−b₁k)x, where the coupling coefficient, k, and amplifiercoefficients are selected such that a₁−b₁k does not equal zero, anda₃−b₃k³ equals zero.

[0098] Similarly, other order nonlinearities can be substantiallyreduced and/or canceled using the foregoing method. In particular, thesecond order nonlinearity can be substantially reduced and/or canceledby selecting most nearly a₂−b₂k²=0, or k=(a₂/b₂)^(1/2). Alternatively,the fourth order nonlinearity can be substantially reduced and/orcanceled by selecting most nearly a₄−b₄k⁴=0, or k=(a₄/b₄)^(1/4). Higherorder nonlinearities of order n can also be substantially reduced and/orcanceled with the same methods by using Taylor series expansions tohigher order terms and most nearly setting k=(a_(n)/b_(n))^(1/n).

[0099] As is well known in the art, the amplifiers shown in FIG. 4 canbe replaced by any other nonlinear device, such as mixers, multi-stageamplifiers, and the like, where such nonlinear devices are similarlycharacterized their Taylor series expansion. Additionally, phaseadjusting means, bias adjusting means and amplitude adjusting means canbe added to provide fine resolution adjustment to more precisely cancelthe undesired nonlinear distortions.

[0100]FIG. 5 is flow diagram that represents a method 500 forsubstantially reducing and/or canceling third order nonlineardistortion, in accordance with an embodiment of the present invention.In the first step, 510, an input signal is split by an input couplingmeans into first and second in-phase coupled signals with the ratio ofthe second coupled signal power, p₂, to the first coupled signal power,p₁, being K=10 log₁₀(p₂/p₁) dB. The first and second signal powers beingtypically defined in milliwatts. As is well known in the art, the inputcoupling means used to split the input signal can be readily designedusing unequal power dividers, resistive networks, hybrids, and the like.

[0101] In the second step, 520 the first coupled signal is processed bya first nonlinear device, such as an amplifier or the like, having again, G₁ dB, and third order output intercept point OIP3₁ dBm and thesecond coupled signal is processed by a second nonlinear device, such asan amplifier or the like, having a gain, G₂ dB, and third order outputintercept point OIP3₂ dBm. Further, the first and second amplifiers andthe input coupling means will have the following relationship, mostnearly 2(OIP3₁−OIP3₂)=3(G₁−G₂−K), where G₁ is not equal to G₂+K. Thecondition 2(OIP3₁−OIP3₂)=3(G₁−G₂−K) is for substantial reduction and/orcancellation of third order nonlinear distortion products. The conditionof G₁ being not equal to G₂+K assures that the linear signal is notcanceled. In typical applications it is desirable that G₁ be muchgreater than G₂+K, such that the linear gain of the overall method 500is not greatly reduced and is approximately equal to G₁, and withsubstantially equal time delay and phase in the two nonlinear signalpaths. As is well known in the art, amplifiers can be designed forvarying levels of distortion, including third order nonlineardistortion, by adjusting current and voltage bias levels of componentswithin the amplifier and by selection or design of the components usedwithin the amplifier.

[0102] In the third step, 530 the output signal of the second amplifier,y₂, is subtracted from the output signal of the first amplifier, y₁ toyield a final output signal, y=y₂−y₁. In effect, the subtractionsubstantially reduces and/or cancels the third order intermodulationdistortion that is present in the output signals of the first and secondamplifiers. The method 500 can be modified to perform the same functionfor third order cancellation by providing for an input coupling meanswhose first and second coupled signals are 180 degrees out of phase andproviding for an adder, as opposed to a subtractor, as the outputcoupling means. Additionally, the alternate steps of phase adjusting,bias adjusting and amplitude adjusting may also be performed inaccordance with method 500 to provide fine resolution adjustment to moreprecisely cancel the undesired nonlinear distortions.

[0103]FIG. 6 is flow diagram that represents an alternate method 600 forsubstantially reducing and/or canceling third order nonlineardistortion, in accordance with an embodiment of the present invention.In the first step, 610, an input signal is split into first and secondin-phase coupled signals at an input coupling means with the ratio ofthe second coupled signal (i.e., voltage, etc.), x₂, to the firstcoupled signal (i.e., voltage, etc.), x₁, being k=x₂/x₁. As is wellknown in the art, the coupling means employed to split the input signalcan be readily designed using unequal power dividers, resistivenetworks, hybrids, and the like. As is also well known in the art,signal currents can be used in place of signal voltages.

[0104] In the second step, 620 the first coupled signal is processed bya first nonlinear device, such as a first amplifier or the like, havinga Taylor series expansion, y₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁ ³+a₄x₁ ⁴ . . . , andthe second coupled signal is processed by a second nonlinear device,such as second amplifier having a Taylor series expansion,y₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . where y₁ and y₂ are the outputsignals (i.e., voltage, etc.), and where x₁ and x₂ are the input signals(i.e., voltage, etc.) of the first and second amplifiers respectively.Further, the first and second amplifiers and the input coupling meanswill have the following relationship, most nearly k=(a_(n)/b_(n))^(1/n)in order to substantially reduce and/or cancel nonlinear distortionproducts of order n, and designed where a₁ is not equal to kb₁. Thecondition that k=(a_(n)/b_(n))^(1/n) is for substantial reduction and/orcancellation of nonlinear distortion products of order n. The conditionof a₁≠kb₁ assures that the linear signal is not canceled. In typicalapplications it is desirable that a₁ be much greater than kb₁, such thatthe linear gain of the overall method 600 is not greatly reduced and isapproximately equal to a₁, and with substantially equal time delay andphase in the two nonlinear devices. As would be apparent to one ofordinary skill in the art, the nonlinear devices may be of differingtype, for example the first nonlinear device may be an amplifier and thesecond nonlinear device may be a diode. As is well known in the art,amplifiers can be designed for varying levels of distortion, includingthird order nonlinear distortion, by adjusting current and voltage biaslevels of components within the amplifier and by selection or design ofthe components used within the amplifier.

[0105] In the third step, 630 the output signal of the second amplifier,y₂, is subtracted from the output signal of the first amplifier, y₁ toyield a final output signal, y=y₂−y₁. In effect, the subtractionsubstantially reduces and/or cancels intermodulation distortion of ordern that is present in the output signals of the first and secondamplifiers. The method 600 can be modified to perform the same functionfor odd values of n by providing for an input coupling means whose firstand second coupled signals are 180 degrees out of phase and providingfor an adder, as opposed to a subtractor, as the output coupling means.Additionally, the alternate steps of phase adjusting, bias adjusting andamplitude adjusting may also be performed as steps of method 600 toprovide fine resolution adjustment to more precisely cancel theundesired nonlinear distortions.

[0106] Another embodiment of the invention is illustrated in theschematic diagram of FIG. 7. An apparatus 170 for substantially reducingand/or canceling nonlinearities includes a nonlinear load 172 andnonlinear device 174. The nonlinear load 172 is designed such that ithas a Taylor series expansion describing the current through thenonlinear load, denoted i_(L), wherei_(L)=a₀+a₁v_(L)+a₂v_(L)+a₃v_(L)+a₄v_(L) ⁴ . . . and where the terminalvoltage of the nonlinear load is denoted as v_(L), the terminal voltagebeing coupled to the final output signal 176. The nonlinear device 174is designed such that it has a Taylor series expansion describing itsoutput current denoted, i₀, where i₀=b₀+b₁v+b₂v²+b₃v³+b₄v⁴ . . . andwhere the input voltage signal 178 is denoted as v. The coefficients a₀,a₁, a₂, a₃, a₄ . . . describe the nonlinear load 172 and coefficientsb₀, b₁, b₂, b₃, b₄ . . . describe the nonlinear device 174. Therefore,i_(L)=i₀ and a₀+a₁v_(L)+a₂v_(L) ²+a₃v_(L) ³+a₄v_(L) ⁴ . . .=b₀+b₁v+b₂v²+b₃v³+b₄v⁴ . . . . As is well known in the art, such Taylorseries expansions are used to describe nonlinear devices as bipolartransistors, field effect transistors, and the like, and are used todescribe such nonlinear load devices as diodes, diode-connectedtransistors, and the like. As is also well known in the art, signalcurrents can be used in place of signal voltages. All ordernonlinearities at the output signal 176 are then substantially reducedand/or canceled from the output signal voltage by providing for thenonlinear device 174 and nonlinear load 172 such that most nearly b₀=a₀,b₁=ca₁, b₂=c²a₂, b₃=c³a₃ . . . b_(n)=c^(n)a_(n) where c is a constant.Under these conditions, the voltage, v_(L), across the nonlinear load172 is most nearly c times the input voltage signal, i.e., v_(L)=cv. Thesmall-signal output signal voltage 176 is 180-degrees phase shifted,i.e., equals −v_(L), if the nonlinear load is connected to a powersupply acting as a small-signal virtual ground. Additionally, phaseadjusting means, bias adjusting means and amplitude adjusting means canbe added to the apparatus 170 to provide fine resolution adjustment tomore precisely cancel the undesired nonlinear distortions.

[0107] Another embodiment of the invention is illustrated in theschematic diagram of FIG. 8. An apparatus 180 for substantially reducingand/or canceling nonlinearities of any order includes a nonlinear loadcomposed of first and second diode-connected n-channel field effecttransistors (FETs), 182 and 184, and a nonlinear device comprised ofn-channel field effect transistor 186. A constant voltage power supplysignal Vdd is present as signal 188. All three transistors 182, 184, and186 are typically designed such that they are near identical devices.Input voltage signal 190 comprises an AC (alternating current) signalvoltage component, in addition to a DC (direct current) bias voltage, asis well known in the art. The AC component of output voltage signal 192is most nearly −2 times (−2×) the AC component of input voltage signal190, with all nonlinear distortion components substantially reducedand/or canceled at the output signal 192. As would be readily apparentto one practiced in the art, other gains may be achieved by using adifferent number of transistors in place of the first and seconddiode-connected, n-channel FETs 182 and 184, or by using scaled lengthsand widths of the gates of field effect transistors in integratedcircuit implementations. For illustration purposes, the FETs are shownas n-channel enhancement-mode metal-oxide semiconductor field effecttransistors. As would be readily apparent to one practiced in the art,the transistors may be implemented using p-channel devices, GaAs fieldeffect transistors, Heterojunction Bipolar Transistors, bipolar junctiontransistors, and the like. Additionally, integrated circuitimplementation may preferentially use transistor devices with eachtransistor's source connected to its own bulk or its own well to avoidbackgate effect.

[0108] Another embodiment of the invention is illustrated in theschematic diagram of FIG. 9. An apparatus 200 for substantially reducingand/or canceling nonlinearities of any order includes a nonlinear loadcomposed of first and second diode-connected npn bipolar junctiontransistors, 202 and 204, and a nonlinear device composed of npn bipolarjunction transistor 206 that are used to substantially reduce and/orcancel nonlinearities of all orders. A constant voltage power supplysignal Vcc is present as signal 208. Input voltage signal 210 includesan AC voltage signal component, in addition to a DC bias voltagecomponent, as is well known in the art. All three transistors 202, 204,and 206 are designed such that they are near identical devices. The ACcomponent of output voltage signal 212 is most nearly −2 times (−2×) theAC component of input voltage signal 210, with all nonlinear distortioncomponents substantially reduced and/or canceled at the output signal212. As would be readily apparent to one practiced in the art, othergains may be achieved by using a different number of transistors inplace of first and second diode-connected npn bipolar junctiontransistors 202 and 204, or by using scaled geometries of bipolartransistors in integrated circuit implementations. It is preferentialfor the currents of all three devices to be more nearly equal, and,thus, for the beta, or current gain, of all three devices 202, 204 and206 to be as large as possible. As would be apparent to one practiced inthe art, the transistors may be implemented using n-channel field effectdevices, p-channel field effect devices, GaAs FET, HeterojunctionBipolar Transistors, and the like. Additionally, phase adjusting means,bias adjusting means and amplitude adjusting means can be added to theapparatus of FIG. 9 to provide fine resolution adjustment to moreprecisely cancel the undesired nonlinear distortions.

[0109]FIG. 10 is flow diagram that represents an alternate method 700for substantially reducing and/or canceling all nonlinear distortion, inaccordance with an embodiment of the present invention. In the firststep, 710, an input voltage, which may also include a DC bias voltage inaddition to AC signal components, is applied to a nonlinear device wherethe current i₀ of the nonlinear device is coupled such that it is equalto the current i_(L) of a nonlinear load. The nonlinear device willprovide for a Taylor series expansion that describes its output currenti₀ as i₀=b₀+b₁v+b₂v²+b₃v³+b₄v⁴ . . . where the input voltage signal isdenoted as v and coefficients b₀, b₁, b₂, b₃, b₄ . . . describe thenonlinear device. As is well known in the art, such Taylor seriesexpansions are used to describe nonlinear devices such as bipolartransistors, field effect transistors and the like.

[0110] At step 720, the output current (i₀) of the nonlinear device iscoupled to a nonlinear load device such that the output current (i₀) isequal to the current (i_(L)) of the non-linear load. The nonlinear loadwill have a Taylor series expansion that relates to the terminalvoltage, denoted v_(L), as i_(L)=a₀+a₁v_(L)+a₂v_(L) ²+a₃v_(L) ³+a₄v_(L)⁴ . . . where current through the nonlinear load is denoted as i_(L) andcoefficients a₀, a₁, a₂, a₃, a₄ . . . describe the nonlinear load. As iswell, known in the art, such Taylor series expansions are used todescribe such nonlinear load devices such as diodes, diode-connectedtransistors and the like. The nonlinear device and the nonlinear loadare provided for such that most nearly b₀=a₀, b₁=ca₁, b₂=c²a₂, b₃=c³a₃ .. . b_(n)=c^(n)a_(n) where c is a constant. Under these conditions, allnonlinear terms and nonlinear signal distortions are substantiallyreduced and/or canceled in the output signal v_(L).

[0111] At step 730, a voltage is output that is taken to be the voltageacross the nonlinear load, v_(L). As noted above, the output signalsubstantially reduces and/or cancels all nonlinear terms and nonlinearsignal distortions. Additionally, the steps of phase adjusting, biasadjusting and amplitude adjusting can be added to provide fineresolution adjustment to more precisely cancel the undesired nonlineardistortions.

[0112]FIG. 11 illustrates a schematic diagram of an apparatus tosubstantially reduce and/or cancel nonlinear distortion, in accordancewith an alternate embodiment of the present invention. The apparatus 220comprises a first nonlinear device, such as first amplifier 222,coupling means 224, a second nonlinear device, such as second amplifier226 and a subtractor 228. In operation, an input signal 230 istransmitted to the first amplifier, the first amplifier provides for aTaylor series expansion describing a first amplified output signal 232(i.e., voltage, etc.), denoted as y₁=a₀+a₁x+a₂x²+a₃x³+a₄x⁴ . . . wherethe input signal (i.e., voltage, etc.) of the first amplifier is denotedas x. The first amplified output signal of the first amplifier is thensplit into first and second in-phase coupled signals 234 and 236 bycoupling means 224. The first in-phase coupled signal 234 (i.e.,voltage, etc.) equals the second in-phase coupled signal 236 (i.e.,voltage, etc.) times a constant factor, k, set by the design of thecoupling means; and for the purpose of illustrating the embodiment, letthe second in-phase coupled signal 236 equal the first amplified outputsignal 232. The second amplifier 226 provides for a Taylor seriesexpansion describing the second amplified output signal 238, denoted asy₂=b₀+b₁(x₂)+b₂(x₂)²+b₃(x₂)³+b₄(x₂)⁴ . . . where the input signal 234 ofthe second amplifier is denoted as x₂. The final output signal 240 isformed by the subtractor 228, where the final output signal 240 is thesecond amplified output signal subtracted from the second in-phasecoupled signal. As is also well known in the art, signal currents can beused in place of signal voltages.

[0113] The coefficients a₀, a₁, a₂, a₃, a₄ . . . describe the firstamplifier 222 and coefficients b₀, b₁, b₂, b₃, b₄ . . . describe thesecond amplifier 226. Third order nonlinearity is then substantiallyreduced and/or canceled in the final output signal 240 by setting thecoupling coefficient k in the circuit such that most nearlya₃−a₃b₁k−2a₁a₂b₂k²−a₁ ³b₃k³=0. Alternatively, second order nonlinearityis substantially reduced and/or canceled in the final output signal bysetting the coupling coefficient k in the circuit such that most nearlya₂−a₂b₁k−a₁ ²b₂k²=0. The desired linear output signal is thenrepresented by the terms a₁x−a₁b₁(kx)=(a₁−a₁b₁k)x, where the couplingcoefficient k and amplifier coefficients are selected such that a₁−a₁b₁kdoes not equal zero. Similarly, higher order nonlinearities of order ncan also be substantially reduced and/or canceled with the same methodsby using Taylor series expansions to higher order terms and solving forthe coefficients of the apparatus in FIG. 11.

[0114] The coupling means 224 can be provided using unequal powerdividers, resistive networks and the like. The subtractor 228 can beprovided using 180 degree hybrids, cross-coupled collectors inintegrated circuit bipolar transistor differential amplifiers,cross-coupled drains in integrated circuit MOSFET (metal oxidesemiconductor field-effect transistor) differential amplifiers, and thelike. The first and second amplifiers shown in FIG. 11 can be replacedby any other nonlinear device, such as mixers, multi-stage amplifiers,and the like, where such devices are similarly characterized theirTaylor series expansion. Additionally, phase adjusting means, biasadjusting means and amplitude adjusting means can be added to theapparatus of FIG. 11 to provide fine resolution adjustment to moreprecisely cancel the undesired nonlinear distortions.

[0115]FIG. 12 illustrates a schematic diagram of an apparatus forsubstantially reducing and/or canceling nonlinearities, in accordancewith an embodiment of the present invention. The apparatus 250 includesa coupling means 252, a first nonlinear device, such as first amplifier254, a subtractor 256 and a second nonlinear device, such as secondamplifier 258. In operation, the input signal 260 is split into firstand second in-phase coupled signals 262 and 264 by coupling means 252.The second in-phase coupled signal 264 is input into first amplifier254. The first amplifier is designed such that it has a Taylor seriesexpansion describing the first amplified output signal 266, denoted asy₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . where the input signal of thefirst amplifier is denoted x₂ and where the second in-phase coupledsignal (i.e., voltage, etc.) equals the first in-phase coupled signal(i.e., voltage, etc.) times a constant factor, k, set by the design ofthe coupling means. The coefficients b₀, b₁, b₂, b₃, b₄, . . . describethe first amplifier. The first in-phase coupled signal 262 and the firstamplified output signal are input into subtractor 256. The subtractorforms subtracted output signal 268 by the subtraction of the firstamplified output signal from the first in-phase coupled signal. Thesubtracted output signal is then input into the second amplifier 258resulting in the ouput of the final output signal 270. The secondamplifier 254 is designed such that it has a Taylor series expansiondescribing the final output signal 270 denoted as y₁, wherey₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁ ³+a₄x₁ ⁴ . . . where the subtracted output signal268 is denoted as x₁. The coefficients a₀, a₁, a₂, a₃, a₄, . . .describe the second amplifier. As is also well known in the art, signalcurrents can be used in place of signal voltages.

[0116] Third order nonlinearity is substantially reduced and/or canceledin the final output signal 270 by setting the coupling coefficient k inthe apparatus such that most nearly2a₂b₁b₂k³−2a₂b₂k²−a₁b₃k³+a₃−3a₃b₁k+3a₃b₁ ²k²−a₃b₁ ³k³=0. Alternatively,second order nonlinearity is substantially reduced and/or canceled inthe final output signal by setting the coupling coefficient k in thecircuit such that most nearly a₂b₁ ²k²−a₁b₂k²−2a₂b₁k+a₂=0. The couplingcoefficient k and amplifier coefficients are selected such that a₁−a₁b₁kdoes not equal zero, i.e., to prevent cancellation of the desired linearterm. Similarly, higher order nonlinearities of order n can also besubstantially reduced and/or canceled with the same methods by usingTaylor series expansions to higher order terms and solving for thecoefficients of the apparatus in FIG. 12. As is well known in the art,the amplifiers shown in FIG. 12 can be replaced by any other nonlineardevice, such as mixers, multi-stage amplifiers, and the like, where suchdevices are similarly characterized their Taylor series expansion.Additonally, phase adjusting means, bias adjusting means and amplitudeadjusting means can be implemented in the apparatus of FIG. 12 toprovide fine resolution adjustment to more precisely cancel theundesired nonlinear distortions.

[0117]FIG. 13 depicts a flow diagram of a method 800 for substantiallyreducing and/or canceling third order nonlinear distortions, inaccordance with an embodiment of the present invention. In the firststep 810, an input signal is transmitted to a first nonlinear device,such as an amplifier, having a Taylor series expansion y₁=a₀+a₁x₁+a₂x₁²+a₃x₁ ³+a₄x₁ ⁴ . . . where y₁ denotes the output (i.e., voltage, etc.)of the first nonlinear device and x₁ denotes the input (i.e., voltage,etc.) of the first nonlinear device. As is well known in the art,nonlinear devices, such as amplifiers, can be designed for varyinglevels of distortion, including third order nonlinear distortion, byadjusting current and voltage bias levels of components within thedevice and by selection or design of the components used within thedevice. As is also well known in the art, signal currents can be used inplace of signal voltages.

[0118] At step 820, the output of the first nonlinear device is split,at a first coupling means, resulting in first and second in-phasecoupled signals. The ratio of the first coupled signal to the secondcoupled signal being k; and for purposes of illustrating the embodiment,the second in-phase coupled signal equals the output of the firstnonlinear device. As is well known in the art, the coupling means can bereadily designed using unequal power dividers, resistive networks, andthe like.

[0119] At step 830, the first coupled output is transmitted to a secondnonlinear device, such as an amplifier, having a Taylor series expansiony₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . where y₂ denotes the output (i.e.,voltage, etc.) of the second nonlinear device and x₂ denotes the input(i.e., voltage, etc.) of the second nonlinear device. The first andsecond nonlinear device and first coupling means may be provided suchthat most nearly a₃−a₃b₁k−2a₁a₂b₂k²−a₁ ³b₃k³=0 to substantially reduceand/or cancel third order distortion products in the final outputsignal. Alternatively, if second order nonlinearity is desired to besubstantially reduced and/or canceled in the final output signal, thecoupling coefficient k will be set in the circuit such that that mostnearly a₂−a₂b₁k−a₁ ²b₂k²=0. In either case of eliminating third orsecond order nonlinear distortion, the coupling coefficient k andnonlinear device coefficients are selected such that a₁−a₁b₁k does notequal zero. Similarly, higher order nonlinearities of order n can alsobe substantially reduced and/or canceled with the same methods by usingTaylor series expansions to higher order terms and solving for thecoefficients of the apparatus in FIG. 11.

[0120] At step 840, the output of the second nonlinear device and thesecond coupled output are coupled, at a second coupling means, resultingin a final output. The final output signal is a result of subtracting,at the second coupling means, the output of the second nonlinear devicefrom the second coupled output signal of the first coupling means. Theintermodulation distortion are then substantially reduced and/orcanceled at the final output signal. As is well known by one practicedin the art, method 800 can be modified to perform the same function withother order nonlinearities by similarly canceling Taylor seriesassociated with order n distortion products. Additionally, a step forphase adjusting, bias adjusting and/or amplitude adjusting can be addedto method 800 to provide fine resolution adjustment to more preciselycancel the undesired nonlinear distortions.

[0121]FIG. 14 illustrates a flow diagram of a method 900 forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention. In the firststep 910, an input signal is transmitted to an input coupling means thatsplits the input signal into first and second in-phase coupled signals,with the ratio of the second coupled signal to the first coupled signalbeing k. As is well known in the art, the coupling means can be readilydesigned using unequal power dividers, resistive networks, and the like.

[0122] At step 920, the second coupled signal is transmitted to a firstnonlinear device, such as an amplifier, having a Taylor series expansiony₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . where y₂ denotes the output of thefirst nonlinear device and x₂ denotes the input of the first nonlineardevice. As is well known in the art, nonlinear devices, such asamplifiers, can be designed for varying levels of distortion, includingthird order nonlinear distortion, by adjusting current and voltage biaslevels of components within the device and by selection or design of thecomponents used within the device. As is also well known in the art,signal currents can be used in place of signal voltages.

[0123] At step 930, the first coupled signal and the output signal ofthe first amplifier is transmitted to a second coupling means tosubtract the output signal of the first amplifier from the first coupledsignal to result in a difference signal.

[0124] At step 940, the difference signal is transmitted to the secondnonlinear device, such as an amplifier, having a Taylor series expansiony₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁ ³+a₄x₁ ⁴ . . . where y₁ denotes the output of thesecond nonlinear device and x₁ denotes the input of the second nonlineardevice. The output of the second nonlinear device being the final outputsignal which is devoid of intermodulation distortion. The first andsecond nonlinear devices and input coupling means are provided such thatmost nearly 2a₂b₁b₂k³−2a₂b₂k²−a₁b₃k³+a₃−3a₃b₁k+3a₃b₁ ²k²−a₃b₁ ³k³=0 tosubstantially reduce and/or cancel third order distortion products inthe final output signal. Alternatively, second order nonlinearity issubstantially reduced and/or canceled in the final output signal bysetting the coupling coefficient k in the circuit such that, most nearlya₂b₁ ²k²−a₁b₂k²−2a₂b₁k+a₂=0. In either case of eliminating third orsecond order nonlinear distortion the coupling coefficient k andamplifier coefficients are selected such that a₁−a₁b₁k does not equalzero.

[0125] As is well known by one practiced in the art, method 900 can bemodified to perform the same function for other order nonlinearities bysimilarly canceling Taylor series terms associated with order ndistortion products. Additionally, the steps of phase adjusting, biasadjusting and amplitude adjusting can be added to method to provide fineresolution adjustment to more precisely cancel the undesired nonlineardistortions.

[0126]FIG. 15 and FIG. 16 show test data for a prototype of theembodiment of FIG. 3. The signal spectrum in FIG. 15 corresponds to thefirst nonlinear device output signal 116 of FIG. 3, where two strongsinusoidal tones at frequencies of 500 megahertz and 500.05 megahertzare visible along with third order intermodulation distortionfrequencies at 499.95 megahertz and 500.1 megahertz. The signal spectrumin FIG. 16 corresponds to the final output signal 120 of FIG. 3, andshows that the third order intermodulation distortion components at499.95 megahertz and 500.1 megahertz have been substantially reducedand/or canceled in the frequency spectrum of the final output signal ofFIG. 3.

[0127]FIG. 17 illustrates a schematic diagram of an apparatussubstantially reducing and/or canceling nonlinear distortions. Theapparatus 280 comprises cross-coupled first and second differentialamplifier subcircuits 282 and 284. The first differential amplifiersubcircuit 282 comprises a first n-channel field-effect transistor (FET)286 and a first differential pair that comprises of a second and thirdn-channel FETs 288 and 290. The first FET has source and well connectedto ground, gate connected to first input bias signal 292 and drainconnected to the sources of the second and third FETs. The first inputbias signal sets the current in the first n-channel FET. The second andthird FETs have sources and wells all connected together and connectedto the drain of the first FET, gates connected to respectivedifferential input signal terminals 294 and 296, and drains connected torespective first and second load resistors 298 and 300 and connected torespective final differential output terminals 302 and 304.

[0128] The second differential amplifier subcircuit 284 comprises afourth n-channel FET 306 and a second differential pair comprised offifth and sixth n-channel FETs 308 and 310. The fourth FET has sourceand well connected to ground, gate connected to second input bias signal312 and drain connected to the sources of the fifth and sixth FETs. Thesecond input bias signal sets the current in fourth FET. The fifth andsixth FETs have sources and wells all connected together and connectedto the drain of the fourth FET, gates connected to respectivedifferential input signal terminals 294 and 296, and drains connected torespective second and first load resistors 300 and 298 and connected torespective final differential output terminals 304 and 302.

[0129] The differential input signal has a positive terminal 294connected to the gates of the second and fifth FETs 288 and 308, and anegative terminal 296 connected to the gates of the third and sixth FETs290 and 310. The first load resistor 298 is connected between the powersupply signal Vdd 314 and the drains of second and sixth FETs 288 and310. The second load resistor 300 is connected between the power supplysignal 314 and the drains of third and fifth FETs 290 and 308. The loadresistor to transistor connections thus comprise a cross-coupled pair ofdifferential amplifiers.

[0130] In effect, the outputs of the first and second differential pairsare subtracted. The final differential output comprises a positive finaldifferential output terminal 304 connected to the drains of the thirdand fifth FETs 290 and 308 and a negative final differential outputterminal 302 connected to the drains of the second and sixth FETstransistor 288 and 310. For illustration purposes, the first, second,third, fourth, fifth and sixth FETs are shown as n-channelenhancement-mode metal-oxide semiconductor field effect transistors.

[0131] For the purpose of illustrating the substantial reduction and/orcancellation of nonlinear distortion in FIG. 17, a simplifiedillustration of the method follows. In the absence of the fourth, fifthand sixth FETs 306, 308 and 310, the first sub-amplifier comprised ofthe first, second and third FETs 286, 288 and 290 and the first andsecond load resistors 298 and 300 can be characterized to have athird-order output intercept point in dBm denoted as OIP3₁, and to havea gain of G₁ dB. In the absence of the first, second and third FETs 286,288 and 290, the second sub-amplifier comprised of the fourth, fifth andsixth FETs 306, 308, and 310 and the first and second load resistors canbe characterized to have a third-order output intercept point in dBmdenoted as OIP3₂ and to have a gain of G₂ dB. As is well known in theart, amplifiers can be designed for varying levels of gain and varyinglevels of distortion, including third-order nonlinear distortion, byadjusting current and voltage bias levels of devices within theamplifier, and by selection or design of the devices (particularlytransistors and resistors) used within the amplifier. For substantiallyreducing and/or canceling third-order nonlinearities in the finaldifferential output 302 and 304, the third-order output intercept pointsof the first sub-amplifier and the second sub-amplifier are designedsuch that most nearly 2(OIP3₁−OIP3₂)=3(G₁−G₂), where OIP3₁ and OIP3₂ arethe third-order output intercept points in dBm of the first and secondsub-amplifiers respectively, and G₁ and G₂ are the gains in dB of thefirst and second sub-amplifiers respectively. Typically, it is desirableto have G₁ much greater than G₂, or G₂ much greater than G₁, so that thegain is not greatly reduced in the overall embodiment of FIG. 17. As iswell known in the art, the parameters OIP3₁, OIP3₂, G₁, and G₂ areestablished by the choice of the input bias signals 292 and 312 and bythe choice of the sizes, geometries, and design of the FETs andresistors.

[0132] As would be readily apparent to one practiced in the art, thefield effect transistors may be implemented using p-channel devices,GaAs field effect transistors, Heterojunction Bipolar Transistors,bipolar junction transistors, and the like. As is also well known in theart, integrated circuit implementation may preferentially use transistordevices with each transistor's source connected to its own bulk or itsown well to avoid backgate effects. Additionally, the firstsub-amplifier and the second sub-amplifier can be replaced by any othercircuit, such as mixers, multi-stage amplifiers, and the like, wheresuch circuits are similarly characterized for gains G₁ and G₂ andcharacterized for third-order output intercept points OIP3₁ and OIP3₂.Also, phase adjusting means, bias adjusting means, and amplitudeadjusting means can be added to the apparatus of FIG. 17 to provide fineresolution adjustment to more precisely cancel the undesired nonlineardistortions.

[0133] As taught by the other methods and apparatus of the presentinvention, the first sub-amplifier and the second sub-amplifier can berepresented by Taylor series expansions and nonlinear distortion oforder, n, substantially reduced and/or canceled by solving for thecoefficient of order, n, at the final differential output terminals, andsetting the coefficient to zero.

[0134] Yet another embodiment of the invention is illustrated in theschematic diagram of FIG. 18. Shown therein is an apparatus 320 forsubstantially reducing and/or canceling nonlinear distortions comprisinga first coupling means 322, first and second nonlinear devices, such asfirst and second amplifiers 324 and 326 and second coupling means 328.The first coupling means 322 splits the input signal 330 into first andsecond in-phase signals 332 and 334. The first coupling means results inthe second in-phase signal being a constant factor, k₁, times the firstin-phase signal. The first in-phase signal is applied as input to thefirst amplifier 324 and the second in-phase signal is applied as inputto the second amplifier 326. A first amplified output signal 336 of thefirst amplifier is combined with a second amplified output signal 338 ofthe second amplifier in the second coupling means 328. The secondcoupling means subtracts the second amplified output signal, multipliedby a constant factor k₂, from the first amplified output signal togenerate the final output signal 340 where k₂ is set by design of thesecond coupling means.

[0135] The first and second amplifiers 324 and 326, and the couplingfactors, k₁ and k₂, of the respective first and second coupling means322 and 324 are designed such that the input signal 330 is notsubstantially reduced and/or canceled in the second coupling means. Inaddition, the first and second amplifiers and the first and secondcoupling means are designed such that one of the nonlinear distortioncomponents, i.e., third-order nonlinear distortion, of the first andsecond amplified output signals 336 and 338 is substantially reducedand/or canceled in the final output signal 340. In the particular caseof substantially reducing and/or canceling third-order distortion in thefinal output signal, the first and second amplifiers and the first andsecond coupling means are designed such that the third-order distortioncomponents are substantially reduced and/or canceled in the final outputsignal.

[0136] As is well known in the art, amplifiers can be designed forvarying levels of distortion, including third-order nonlineardistortion, by adjusting current and voltage bias levels of componentswithin the amplifier and by selection or design of the components usedwithin the amplifier. In addition, the first and second coupling meanscan be readily designed by one practiced in the art using unequal powerdividers, resistive networks, and the like. In addition, the secondcoupling means can be readily designed by one practiced in the art usingcross-coupled collectors in integrated circuit bipolar transistordifferential amplifiers, cross-coupled drains in integrated circuitmetal-oxide field-effect transistor differential amplifiers, and thelike.

[0137] For substantially reducing and/or canceling of third-ordernonlinearities in the final output signal 340 the third-order outputintercept points of the first and second amplifiers 324 and 326 aredesigned such that most nearly 2(OIP3₃₂₄−OIP3₃₂₆−K2)=3(G₃₂₄−G₃₂₆−K1−K2),where OIP3₃₂₄ and OIP3₃₂₆ are the third-order output intercept points indBm of the first and second amplifiers, respectively, and G₃₂₄ and G₃₂₆are the gains in dB of the first and second amplifiers, respectively.Additionally, K1=10 log₁₀(p₃₃₄/p₃₃₂) where p₃₃₂ and p₃₃₄ are the powerlevels in milliwatts of the first and second in-phase signals 332 and334, respectively, and K2=20 log₁₀(k₂), where k₂ is the aforementionedmultiplicative factor established by the second coupling means.Typically, it is desirable to have G₃₂₄ much greater than G₃₂₆+K1+K2, orG₃₂₆+K1+K2 much greater than G₃₂₄, SO that the gain is not greatlyreduced in the overall embodiment of FIG. 18, and with substantiallyequal time delay and phase in the two amplifiers. The amplifiers shownin FIG. 18 can be replaced by any other nonlinear device, such asmixers, multi-stage amplifiers, and the like, where such devices aresimilarly characterized for gains G₃₂₄ and G₃₂₆ and third-order outputintercept points OIP3₃₂₄ and OIP3₃₂₆. As would be apparent to onepracticed in the art, the nonlinear devices may be of differing type,for example the first nonlinear device may be an amplifier and thesecond nonlinear device may be a diode. Additionally, phase adjustingmeans, bias adjusting means, and amplitude adjusting means can be addedto the apparatus of FIG. 18 to provide fine resolution adjustment tomore precisely cancel the undesired nonlinear distortions.

[0138] Another embodiment of the invention is illustrated in theschematic diagram of Figure FIG. 18, as previously described, exceptthat the amplifiers are designed to substantially reduce and/or cancelnonlinearities of any order. The first amplifier 324 is designed suchthat it has a Taylor series expansion describing the first amplifiedoutput signal 336 denoted as y₁=a₀+a₁x+a₂x²+a₃x³+a₄x⁴ . . . , where thefirst amplified output signal is denoted y₁, and the first in-phasesignal 332, being the input to the first amplifier, is denoted as x. Thesecond amplifier 326 is designed such that it has a Taylor seriesexpansion describing its output, the second amplified output signal 338denoted as y₂=b₀+b₁(k₁x)+b₂(k₁x)²+b₃(k₁x)³+b₄(k₁x)⁴ . . . , where thesecond amplified output signal 338 is denoted y₂ and the second in-phasesignal 334 is denoted k₁x since the second in-phase signal (i.e.,voltage, etc.) equals the first in-phase signal (i.e., voltage, etc.)times a constant factor, k₁, where k₁ is set by the design of the firstcoupling means 322. The final output is formed by the second couplingmeans 328 to generate the final output signal 340 that is thesubtraction of the second amplified output signal times a constantfactor k₂, set by the second coupling means, from the first amplifiedoutput signal. The coefficients a₀, a₁, a₂, a₃, a₄, . . . describe thefirst amplifier and coefficients b₀, b₁, b₂, b₃, b₄, . . . describe thesecond amplifier.

[0139] Third-order nonlinearity is substantially reduced and/or canceledin the final output signal 340 by setting the coupling coefficients k₁and k₂ in the circuit such that most nearly a₃−k₂b₃k₁ ³=0. The desiredlinear output signal is then determined by the termsa₁x−k₂b₁(k₁x)=(a₁−k₂b₁k₁)x, where the coupling coefficients k₁ and k₂and amplifier coefficients are selected such that (a₁−k₂b₁k₁) does notequal zero, and that a₃−k₂b₃k₁ ³ equals zero. Similarly, other ordernonlinearities can be substantially reduced and/or canceled using theforegoing method. In particular, the second-order nonlinearity can besubstantially reduced and/or canceled by selecting most nearly a₂−k₂b₂k₁²=0. Alternatively, the fourth order nonlinearity can be substantiallyreduced and/or eliminated by selecting most nearly a₄−k₂b₄k₁ ⁴=0. Higherorder nonlinearities of order n can also be substantially reduced and/orcanceled with the same methods by using Taylor series expansions tohigher order terms and setting most nearly a_(n)−k₂b_(n)k₁ ^(n)=0. Theamplifiers shown in FIG. 18 can be replaced by any other nonlineardevice, such as mixers, multi-stage amplifiers, and the like, where suchcircuits are similarly characterized their Taylor series expansion.Additionally, phase adjusting means, bias adjusting means, and amplitudeadjusting means can be added to the apparatus to provide fine resolutionadjustment to more precisely cancel the undesired nonlinear distortions.

[0140]FIG. 19 illustrates a schematic diagram of an apparatus 350 forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention. The apparatus350 comprises a first coupling means 352, first and second nonlineardevices, such as first and second amplifiers 354 and 356, adaptivecontrol and feedback means 358 and second coupling means 360. The firstcoupling means 352 splits the input signal 362 into first and secondin-phase signals 364 and 366. The first coupling means results in thesecond in-phase signal that is a constant factor, k₁, times the firstin-phase signal. The first in-phase signal is applied as input to thefirst amplifier 354 and the second in-phase signal is applied as inputto the second amplifier 356. A first amplified output signal 368 of thefirst amplifier is combined with a second amplified output signal 370 ofthe second amplifier in the second coupling means 360. The secondcoupling means subtracts the second amplified output signal, multipliedby a constant factor, k₂, from the first amplified output signal togenerate the final output signal 372.

[0141] Also shown in the FIG. 19 embodiment is adaptive control andfeedback means 358 with feedback input from the final output signal 372and with output control signals 374, 376, 378, and 380 where the outputcontrol signals adaptively adjust the phase, amplitude, andnonlinearities of the first coupling means 352, the first amplifier 354,the second amplifier 356, and the second coupling means 360 in order toprovide fine resolution adjustment to more precisely cancel theundesired nonlinear distortions by monitoring the final output signaland adjusting control signals. As is well known in the art, the feedbackinput, comprising the final output signal, can be alternatively takenfrom more advantageous signal points in larger systems incorporating theembodiment of FIG. 19, such signal points including bit error ratesignals and the like.

[0142] The first and second amplifiers 354 and 356 and the couplingfactors, k₁ and k₂, of the first and second coupling means 352 and 360are designed such that the input signal 362 is not canceled andeliminated in the second coupling means. In addition, the first andsecond amplifiers and the first and second coupling means are designedsuch that one of the nonlinear distortion components, i.e., third-ordernonlinear distortion, of the first and second amplified output signals368 and 370 is substantially reduced and/or canceled in the final outputsignal 372. In the particular case of substantially reducing and/orcanceling third-order distortion in the final output signal, the firstand second amplifiers and the first and second coupling means aredesigned such that the third-order distortion components aresubstantially reduced and/or canceled in the final output signal.

[0143] As is well known in the art, first and second amplifiers 354 and356 can be designed for varying levels of distortion, includingthird-order nonlinear distortion, by adjusting current and voltage biaslevels of components within the amplifier and by selection or design ofthe components used within the amplifier. In addition, the first andsecond coupling means 352 and 360 can be readily designed by onepracticed in the art using unequal power dividers, resistive networks,and the like. In addition, the second coupling means can be readilydesigned by one practiced in the art using cross-coupled collectors inintegrated circuit bipolar transistor differential amplifiers,cross-coupled drains in integrated circuit metal-oxide field-effecttransistor differential amplifiers, and the like.

[0144] For substantially reducing and/or canceling of third-ordernonlinearities in the final output signal 372 in the embodiment of FIG.19, the third-order output intercept points of the first and secondamplifiers 354 and 356 are designed such that most nearly2(OIP3₃₅₄−OIP3₃₅₆−K2)=3(G₃₅₄−G₃₅₆−K1−K2), where OIP3₃₅₄ and OIP3₃₅₆ arethe third-order output intercept points in dBm of the first and secondamplifiers, respectively, and G₃₅₄ and G₃₅₆ are the gains in dB of thefirst and second amplifiers, respectively. Additionally, K1=10log₁₀(p₃₆₆/p₃₆₄) where p₃₆₄ and p₃₆₆ are the power levels in milliwattsof the first and second in-phase signals 364 and 366, respectively, andK2=20 log₁₀(k₂), where k₂ is the aforementioned multiplicative factorestablished by the second coupling means. Typically, it is desirable tohave G₃₅₄ much greater than G₃₅₆+K1+K2, or G₃₅₆+K1+K2 much greater thanG₃₅₄, so that the gain is not greatly reduced in the overall embodimentof FIG. 19, and with substantially equal time delay and phase in the twoamplifiers.

[0145] The amplifiers shown in FIG. 19 can be replaced by any othernonlinear device, such as mixers, multi-stage amplifiers, and the like,where such nonlinear devices are similarly characterized for gains G₃₅₄and G₃₅₆ and third-order output intercept points OIP3₃₅₄ and OIP3₃₅₆.Additionally, phase adjusting means, bias adjusting means, and amplitudeadjusting means can be added to the apparatus of FIG. 19 to provide fineresolution adjustment to more precisely cancel the undesired nonlineardistortions.

[0146] Another embodiment of the invention is illustrated in theschematic diagram of FIG. 20. Shown therein is an apparatus 400 forsubstantially reducing and/or canceling nonlinear distortion comprisingfirst, second, third, and fourth nonlinear devices, such as first,second, third and fourth amplifiers, 402, 404, 406 and 408, andattenuator 410 and first and second subtractors 412 and 414. Inoperation, an input signal 420 is applied both to the first and secondamplifiers 402 and 404, where the time delay and phase of the secondamplifier substantially equals the time delay and phase of the firstamplifier. The first amplified output signal 422 of the first amplifieris attenuated by the attenuator 410. The second amplified output signal424 of the second amplifier is subtracted from the attenuated outputsignal 426 of the attenuator in the first subtractor 412 resulting indifference output signal 428. The first amplified output signal 422 ofthe first amplifier is also input to the third amplifier 406 whose timedelay and phase substantially equals the time delay and phase of thefourth amplifier 408 that amplifies the difference output signal 428.The fourth amplified output signal 430 of the fourth amplifier issubtracted from the third amplified output signal 432 of the thirdamplifier in the second subtractor 414 to form the final output signal434.

[0147] For illustrative purposes, an example input frequency spectrum440 is shown for input signal 420 comprised of two input spectral linesof equal amplitude at different frequencies. The second spectrum at thefirst amplified output signal 422 of the first amplifier 402 isillustrated in second spectrum 442 where the two innermost spectrallines correspond to the original input frequencies illustrated in theinput spectrum 440, but with larger amplitude, and the two outermostspectral lines represent third-order distortion components of the firstamplified output signal. The third spectrum at the difference outputsignal 428 at the output of the first subtractor 412 is illustrated inthird spectrum 444 where the two outermost spectral lines correspond toan attenuated version of the third-order distortion components ofspectrum 442 (the two outermost spectral lines in spectrum 442) lessthird-order distortion components of the second amplified output signal424 of the second amplifier 404, and the attenuation of attenuator 410is adjusted to preferentially, but not necessarily, greatly reduce thetwo innermost spectral components of second spectrum 442 relative to thethird-order distortion components of second spectrum 442, these twoinnermost spectral components appearing greatly reduced in thirdspectrum 444 relative to the outermost spectral components. The methodis distinct from the prior art of FIG. 1 in that it allows for a widelyvarying range of the input spectral components (the two innermostspectral components) in the third spectrum at the difference outputsignal 428, and allows for the input spectral components to be largerthan the third-order distortion components, although not illustrated assuch. The fourth spectrum at the fourth amplified output signal 430 ofthe fourth amplifier 408 is illustrated in fourth spectrum 446 where thespectral lines correspond to an amplified version of third spectrum 444.The fifth spectrum at the final output signal 434 of the secondsubtractor 414 is illustrated in fifth spectrum 448 where the twospectral lines correspond to an amplified version of the input spectrum440 and all distortion products in second spectrum 442 (the twooutermost spectral lines in second spectrum 442) are canceled andeliminated as shown in fifth spectrum 448.

[0148] As taught by the other methods and apparatus of this invention,the third order intermodulation components are substantially reducedand/or canceled in the final output signal 434 by proper design andselection of the attenuation of the attenuator 410, and the gains,nonlinearity, and intercept points of the first, second, third andfourth amplifiers 402, 404, 406 and 408. For example, the first, second,third and fourth amplifiers 402, 404, 406 and 408 can be represented asTaylor series expansions, the attenuator represented as a constantcoefficient, and nonlinear distortion of order, n, canceled by solvingfor the coefficient of order, n, at the final output signal 434, andsetting this coefficient to zero. Additionally, phase adjusting means,bias adjusting means, and amplitude adjusting means can be added to theapparatus of FIG. 20 to provide fine resolution adjustment to moreprecisely cancel the undesired nonlinear distortions. As is also evidentby other methods and apparatus in the invention, the embodiment of FIG.20 can also be used to substantially reduce and/or cancel nonlinearitiesof any order by using Taylor series expansions for the amplifiers and byproper design and selection of the attenuation of the attenuator 410,and the gains, nonlinearity, and Taylor series expansion coefficients ofthe first, second, third and fourth amplifiers 402, 404, 406 and 408.Additionally, the amplifiers shown in FIG. 20 can be replaced by anyother nonlinear device, such as mixers, multi-stage amplifiers, and thelike, where such nonlinear devices are similarly characterized forgains, nonlinearities, and third-order output intercept point. Further,the embodiment of FIG. 20 may be found preferential in power amplifierapplications, where the third amplifier 406 is the high power amplifier.

[0149] For the purpose of illustration in FIG. 20, assume the firstnonlinear device is provided such that it has a Taylor series expansiondescribing the output signal (i.e., voltage, etc.) of the firstnonlinear device, y₁, in terms of an input signal (i.e., voltage, etc.)of the first nonlinear device, x₁, as y₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁ ³+a₄x₁ ⁴ .. . The second nonlinear device is provided such that it has a Taylorseries expansion describing the output signal of the second nonlineardevice, y₂, in terms of an input signal of the second nonlinear device,x₂, as y₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ . . . The third nonlinear deviceis provided such that it has a Taylor series expansion describing theoutput signal of the third nonlinear device, y₃, in terms of an inputsignal of the third nonlinear device, x₃, as y₃=c₀+c₁x₃+c₂x₃ ²+c₃x₃³+c₄x₃ ⁴ . . . The fourth nonlinear device is provided such that it hasa Taylor series expansion describing the output signal of the fourthnonlinear device, y₄, in terms of an input signal of the fourthnonlinear device, x₄, as y₄=d₀+d₁x₄+d₂x₄ ²+d₃x₄ ³+d₄x₄ ⁴ . . . Theratio, k, is provided such that k equals the ratio of the output (i.e.,voltage, etc.) of the attenuator to the input (i.e., voltage, etc.) ofthe attenuator. Third order nonlinear distortion is substantiallyreduced and/or canceled by setting most nearly b₁³d₃+b₃d₁+2a₁b₂d₂k−2b₁b₂d₂−2a₁a₂d₂k²+3a₁ ²b₁d₃k²−3a₁b₁ ²d₃k−a₁³d₃k³+2a₁a₂c₂+a₁ ³c₃+a₃c₁+2a₂b₁d₂k−a₃d₁k=0, and such thatb₁d₁+a₁c₁−a₁d₁k≠0 so that the desired linear output is not canceled.Similarly, second order nonlinear distortion is substantially reducedand/or canceled by setting b₂d₁+a₁ ²c₂−b₁ ²d₂+2a₁b₁d₂k+a₂c₁−a₁²d₂k²−a₂d₁k=0, and such that b₁d₁+a₁c₁−a₁c₁−a₁d₁k≠0 so that the desiredlinear output is not canceled.

[0150] As taught by the other methods and apparatus of the presentinvention, an input coupling means may be used in FIG. 20 to split theinput signal into a first and second coupled signal, said second coupledsignal in-phase and attenuated relative to the first coupled signal,with the first coupled signal applied as input to the first nonlineardevice 402, and the second coupled signal applied as input to the secondnonlinear device 404. In addition, subtractor 414 in FIG. 20 may bereplaced by a second coupling means, the second coupling means combiningthe output signal of the third nonlinear device 406 with a 180-degreephase-shifted and attenuated version of the output signal of the fourthnonlinear device 408. Similarly, subtractor 412 may replaced with athird coupling means. As taught by the other methods and apparatus ofthe present invention, after such modifications the third orderintermodulation components are substantially reduced and/or canceled inthe final output signal 434 by proper design and selection of thecoupling coefficients of the aforementioned input coupling means, secondcoupling means, third coupling means, the attenuation of the attenuator410, and the gains, nonlinearity, and intercept points of the first,second, third and fourth nonlinear devices 402, 404, 406 and 408.

[0151] As taught by other embodiments of the present invention, adaptivecontrol means may be added to the apparatus embodiment of FIG. 20 toadaptively adjust the gain, phase, and nonlinearity of the first,second, third, and fourth nonlinear devices, and adjust the attenuationof the attenuator, based on feedback to the adaptive control means fromthe final output signal, or alternatively based on feedback from moreadvantageous signal points in larger systems, such as bit error ratesignals and the like.

[0152]FIG. 21 illustrates a flow diagram of a method 950 forsubstantially reducing and/or canceling nonlinear distortion, inaccordance with an embodiment of the present invention. In the firststep 952, an input signal is transmitted to an input coupling means thatsplits the input signal into first and second in-phase coupled signals.As is well known in the art, the coupling means can be readily designedusing unequal power dividers, resistive networks, and the like. At step954, the first coupled signal is transmitted to a first nonlineardevice, such as an amplifier, having a Taylor series expansiondescribing the output signal (i.e., voltage, etc.) of the firstnonlinear device, y₁, in terms of an input signal (i.e., voltage, etc.)of the first nonlinear device, x₁, as y₁=a₀+a₁x₁+a₂x₁ ²+a₃x₁ ³+a₄x₁ ⁴ .. . At step 956, the second coupled signal is transmitted to a secondnonlinear device, such as an amplifier, having a Taylor series expansiondescribing the output signal (i.e., voltage, etc.) of the secondnonlinear device, y₂ in terms of an input signal (i.e., voltage, etc.)of the second nonlinear device, x₂, as y₂=b₀+b₁x₂+b₂x₂ ²+b₃x₂ ³+b₄x₂ ⁴ .. . , and with substantially equal time delay and phase in the first andsecond nonlinear devices. As is well known in the art, nonlineardevices, such as amplifiers, can be designed for varying levels ofdistortion, including third order nonlinear distortion, by adjustingcurrent and voltage bias levels of components within the device and byselection or design of the components used within the device. As is alsowell known in the art, signal currents can be used in place of signalvoltages.

[0153] At step 958, the output signal of the first nonlinear device istransmitted to an attenuator with output signal, k, times attenuatorinput signal, and, at step 960, the output signal of the secondnonlinear device is subtracted from attenuator output to form adifference signal.

[0154] At step 962, the output of the first nonlinear device istransmitted to third nonlinear device, such as an amplifier, with Taylorseries expansion describing the output signal (i.e., voltage, etc.) ofthe third nonlinear device, y₃, in terms of an input signal (i.e.,voltage, etc.) of the third nonlinear device, x₃, as y₃=c₀+c₁x₃+c₂x₃²+c₃x₃ ³+c₄x₃ ⁴ . . . At step 964, the difference signal is transmittedto a fourth nonlinear device, such as an amplifier, with Taylor seriesexpansion describing the output signal (i.e., voltage, etc.) of thefourth nonlinear device, y₄, in terms of an input signal (i.e., voltage,etc.) of the fourth nonlinear device, x₄, as y₄=d₀+d₁x₄+d₂x₄ ²+d₃x₄³+d₄x₄ ⁴ . . . , and with substantially equal time delay and phase inthe third and fourth nonlinear devices.

[0155] At step 966, the output of the fourth nonlinear device issubtracted from the output of the third nonlinear device to form adifference signal (i.e., voltage, etc.) defined as the final outputsignal, substantially reducing and/or canceling nonlinear distortion.The relationship between the attenuator, first, second, third, andfourth nonlinear devices being defined such that third order nonlineardistortion is substantially reduced and/or canceled by setting mostnearly b₁ ³d₃+b₃d₁+2a₁b₂d₂k−2b₁b₂d₂−2a₁a₂d₂k²+3a₁ ²b₁d₃k²−3a₁b₁ ²d₃k−a₁³d₃k³+2a₁a₂c₂+a₁ ³c₃+a₃c₁+2a₂b₁d₂k−a₃d₁k=0, and such that b₁d₁+a_(c)₁−a₁d₁k≠0 so that the desired linear output is not canceled.Alternatively, second order nonlinear distortion is canceled andeliminated by most nearly setting b₂d₁+a₁ ²c₂−b₁ ²d₂+2a₁b₁d₂k+a₂c₁−a₁²d₂k²−a₂d₁k=0, and such that b₁d₁+a₁c₁−a₁d₁k≠0 so that the desiredlinear output is not canceled.

[0156] As is well known by one practiced in the art, method 950 can bemodified to perform the same function for other order nonlinearities bysimilarly canceling Taylor series terms associated with order ndistortion products. Additionally, the steps of phase adjusting, biasadjusting and amplitude adjusting can be added to method 950 to providefine resolution adjustment to more precisely cancel the undesirednonlinear distortions.

[0157] As taught by other embodiments of the present invention, the stepof adjusting, adaptively, the gain, phase, and nonlinearity of thefirst, second, third, and fourth nonlinear devices may alternativelycomprise the method detailed by FIG. 21. Additionally, the step ofadjusting, adaptively, the attenuation of the attenuator may comprisethe method detailed by FIG. 21. The adaptive adjustment will typicallyoccur based on feedback to the adaptive control means from the finaloutput signal, or alternatively based on feedback from more advantageoussignal points in larger systems, such as bit error rate signals and thelike.

[0158] Many modifications and other embodiments of the invention willcome to mind to one skilled in the art to which this invention pertainshaving the benefit of the teachings presented in the foregoingdescriptions and the associated drawings. Therefore, it is to beunderstood that the invention is not to be limited to the specificembodiments disclosed and that modifications and other embodiments areintended to be included within the scope of the appended Claims.Although specific terms are employed herein, they are used in a genericand descriptive sense only and not for purposes of limitation.

That which is claimed:
 1. An apparatus for substantially reducingnonlinear distortion, the apparatus comprising: a nonlinear devicehaving an input and an output, the nonlinear device having a Taylorseries expansion describing an output current, i₀, in terms of an inputvoltage, v, as i₀=b₀+b₁v+b₂v²+b₃v³+b₄v⁴ . . . ; and a nonlinear loadhaving an input in communication with the output of the nonlinear deviceand in communication with a final output, the nonlinear load has aTaylor series expansion describing a current through the nonlinear load,i_(L), in terms of a terminal voltage, v_(L), asi_(L)=a₀+a₁v_(L)+a₂v_(L) ²+a₃v_(L) ³+a₄v_(L) ⁴, such that the nonlineardevice and the nonlinear load are provided such that most nearly b₀=a₀,b₁=ca₁, b₂=c²a₂, b₃=c³a₃, b_(n)=c^(n)a_(n) where, c, is a constant,wherein the output of the nonlinear device substantially reducesnonlinearities of the nonlinear device and the nonlinear load.
 2. Theapparatus of claim 1, wherein the nonlinear device further comprises: afirst n-channel field effect transistor (FET) having a gate incommunication with an input source, a source and well in communicationwith ground, and a drain in electrical communication with an output, andwherein the nonlinear load further comprises: a second n-channel FEThaving a source and well in electrical communication with the drain ofthe first n-channel FET, and a gate and drain in common electricalcommunication; and a third n-channel FET having a source and well inelectrical communication with the drain of the second n-channel FET, anda gate and drain in common electrical communication with a power supply.3. The apparatus of claim 1, wherein the nonlinear device furthercomprises: a first npn bipolar junction transistor (BJT) having a basein electrical communication with an input source, an emitter inelectrical communication with ground and a collector in electricalcommunication with an output, and wherein the nonlinear load furthercomprises: a second npn BJT having an emitter in electricalcommunication with the collector of the first npn BJT, and a base andcollector in common electrical communication; and a third npn BJT havingan emitter in electrical communication with a collector of the secondnpn BJT, and a base and collector in common electrical communicationwith a power supply.
 4. A method for substantially reducing nonlineardistortion in an apparatus, the method comprising the steps of: applyingan input voltage to a nonlinear device, the nonlinear device having aTaylor series expansion describing an output current, i_(o), in terms ofan input voltage, v, as i₀=b₀+b₁v+b₂v²+b₃v³+b₄v⁴ . . . ; coupling anoutput current of the nonlinear device to a nonlinear load, thenonlinear load having a Taylor series expansion describing currentthrough the nonlinear load, i_(L), in terms of a terminal voltage,v_(L), as i_(L)=a₀+a₁v_(L)+a₂v_(L) ²+a₃v_(L) ³+a₄v_(L) ⁴ . . . , and thenonlinear device and the nonlinear load are provided such that mostnearly b₀=a₀, b₁=ca₁, b₂=c² a₂, b₃=c³a₃, . . . , b_(n)=c^(n)a_(n) where,c, is a constant; and outputting the terminal voltage at the nonlinearload to substantially reduce nonlinear terms and nonlinear signaldistortion.